US20110211658A1 - System and method of performing digital multi-channel audio signal decoding - Google Patents
System and method of performing digital multi-channel audio signal decoding Download PDFInfo
- Publication number
- US20110211658A1 US20110211658A1 US13/069,090 US201113069090A US2011211658A1 US 20110211658 A1 US20110211658 A1 US 20110211658A1 US 201113069090 A US201113069090 A US 201113069090A US 2011211658 A1 US2011211658 A1 US 2011211658A1
- Authority
- US
- United States
- Prior art keywords
- signal
- digital
- audio signal
- channel
- coefficient
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Abandoned
Links
Images
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N7/00—Television systems
- H04N7/06—Systems for the simultaneous transmission of one television signal, i.e. both picture and sound, by more than one carrier
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
- H04N21/80—Generation or processing of content or additional data by content creator independently of the distribution process; Content per se
- H04N21/81—Monomedia components thereof
- H04N21/8106—Monomedia components thereof involving special audio data, e.g. different tracks for different languages
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N21/00—Selective content distribution, e.g. interactive television or video on demand [VOD]
- H04N21/80—Generation or processing of content or additional data by content creator independently of the distribution process; Content per se
- H04N21/85—Assembly of content; Generation of multimedia applications
- H04N21/854—Content authoring
- H04N21/85406—Content authoring involving a specific file format, e.g. MP4 format
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/44—Receiver circuitry for the reception of television signals according to analogue transmission standards
- H04N5/60—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals
- H04N5/602—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals for digital sound signals
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
- H04N5/00—Details of television systems
- H04N5/44—Receiver circuitry for the reception of television signals according to analogue transmission standards
- H04N5/60—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals
- H04N5/607—Receiver circuitry for the reception of television signals according to analogue transmission standards for the sound signals for more than one sound signal, e.g. stereo, multilanguages
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
- H04R5/00—Stereophonic arrangements
- H04R5/04—Circuit arrangements, e.g. for selective connection of amplifier inputs/outputs to loudspeakers, for loudspeaker detection, or for adaptation of settings to personal preferences or hearing impairments
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04H—BROADCAST COMMUNICATION
- H04H20/00—Arrangements for broadcast or for distribution combined with broadcast
- H04H20/44—Arrangements characterised by circuits or components specially adapted for broadcast
- H04H20/46—Arrangements characterised by circuits or components specially adapted for broadcast specially adapted for broadcast systems covered by groups H04H20/53-H04H20/95
- H04H20/47—Arrangements characterised by circuits or components specially adapted for broadcast specially adapted for broadcast systems covered by groups H04H20/53-H04H20/95 specially adapted for stereophonic broadcast systems
- H04H20/48—Arrangements characterised by circuits or components specially adapted for broadcast specially adapted for broadcast systems covered by groups H04H20/53-H04H20/95 specially adapted for stereophonic broadcast systems for FM stereophonic broadcast systems
Definitions
- Certain embodiments of the present invention relate to the processing of multi-channel television signals. More specifically, certain embodiments relate to a system and method for digitally decoding BTCS (Broadcast Television System Committee) audio signals.
- BTCS Broadcast Television System Committee
- the FCC adopted the BTSC format as a standard for multi-channel television sound (MTS).
- MTS multi-channel television sound
- the BTSC format is used with a composite TV signal that includes a video signal as well as the BTSC format for the sound reproduction.
- the BTSC format is similar to FM stereo but has the ability to carry two additional audio channels.
- Left plus right (L+R) channel mono information is transmitted in a way similar to stereo FM in order to ensure compatibility with monaural television receivers.
- a 15.734 KHz pilot signal is used, instead of the FM stereo 19 KHz pilot signal, which allows the pilot signal to be phase-locked to the horizontal line frequency.
- a double sideband-suppressed carrier at twice the frequency of the pilot transmits the left minus right (L ⁇ R) stereo information.
- the stereo information is DBX encoded to aid in noise reduction.
- An SAP channel is located at 5 times the pilot frequency.
- the SAP channel may be used for second language or independent source program material.
- a professional audio channel may be added at 6.5 times the pilot frequency in order to accommodate additional voice or data.
- Stereo tuners and demodulator units capable of decoding the BTSC format have been on the market for some time.
- the front end of the units typically includes analog components or integrated circuit chips.
- BTSC decoding has been done in the analog domain requiring larger, more expensive implementations that consume a significant amount of power.
- Previous digital implementations may not be optimized, requiring many clock cycles to perform various processing functions.
- An embodiment of the present invention provides efficient, low cost digital multi-channel audio signal decoding of BTSC audio signals in the digital domain.
- several stages of digital signal processing are used where each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage.
- Efficient pipelined processing is used to execute the various processing functions in order to reduce clock cycles and addressing to memory.
- a method for performing digital multi-channel decoding of a DBX-encoded composite audio signal is provided. Each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage.
- Analog-to-digital conversion of the composite audio signal is performed first to generate a composite digital audio signal. After analog-to-digital conversion, all signal processing may be performed in the digital domain.
- the composite digital audio signal is digitally filtered to compensate for uneven frequency response caused by previous stages of processing, including IF demodulation.
- Digital channel demodulation and filtering are performed to isolate single channels of the composite digital audio signal such as SAP, L ⁇ R, and L+R channels.
- SAP and L ⁇ R channels are DBX decoded resulting in corresponding decoded signals using a unique combination of digital filters that are an efficient translation of a corresponding combination of analog filters.
- the decoded L ⁇ R channel and the L+R channel are re-matrixed to form left and right stereo signals. Any of the SAP signal, left and right stereo signals, and L+R channel signal may be sample rate converted and output at a standard audio output rate.
- a system is provided on an ASIC chip for performing digital multi-channel audio signal decoding.
- the system comprises a sigma-delta analog-to-digital (A/D) conversion block operating on a composite analog audio signal to generate a composite digital audio signal, a clock generation block generating a master clock signal and other clock signals used in the multi-channel audio signal decoding process, and a DSP processing block including a five-stage pipelined data path performing certain digital multi-channel audio signal processing functions in response to a set of instructions.
- A/D analog-to-digital
- the system further includes an input buffer block connected between the sigma-delta A/D conversion block and the DSP processing block to transfer the composite digital audio signal to the DSP processing block, a configuration register block interfacing to the DSP processing block, the input buffer block, and the sigma-delta A/D conversion block, and an output buffer block interfacing to the DSP processing block and the clock generation block to output standard audio output signals at standard audio output rates.
- the five-stage pipelined data path comprises a memory address calculation stage, a memory data fetch stage, a multiplication stage, an accumulation/mantissa-generation/signal-shifter stage, and a registers/memory-write stage.
- Certain embodiments of the present invention afford an approach to achieve efficient, low cost digital multi-channel audio signal decoding of BTSC audio signals in the digital domain. Certain embodiments of the present invention use several stages of digital signal processing where each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage.
- FIG. 1 is an illustration of the various components of a composite audio signal to be decoded in accordance with an embodiment of the present invention.
- FIG. 2A is a schematic functional block diagram of the decoding method used to decode the composite audio signal of FIG. 1 in accordance with an embodiment of the present invention.
- FIG. 2B is a schematic functional block diagram of pilot signal detection and DSB demodulation performed in the method of FIG. 2A in accordance with an embodiment of the present invention.
- FIG. 3A is a schematic functional block diagram of a combination of digital filter transfer functions used to perform DBX decoding in accordance with an embodiment of the present invention.
- FIG. 3B is a schematic functional block diagram of a transfer function of FIG. 3A in accordance with an embodiment of the present invention.
- FIG. 4 illustrates the translated analog and digital transfer function equations corresponding to the DBX decoding performed in FIG. 3A in accordance with an embodiment of the present invention.
- FIG. 5 is a schematic block diagram of a decoding system implemented on an ASIC chip and used to implement the decoding method of FIG. 2A in accordance with an embodiment of the present invention.
- FIG. 6 is a flowchart illustration of the data path processing performed by the pipelined decoding system of FIG. 5 in accordance with an embodiment of the present invention.
- FIG. 7 is a table of instructions that may be implemented by the data path processing of FIG. 6 in accordance with an embodiment of the present invention.
- FIG. 1 is an illustration of the various components of a BTSC composite audio signal 10 to be decoded in accordance with an embodiment of the present invention.
- the FCC adopted the BTSC format as a standard for multi-channel television sound (MTS).
- the BTSC format is used with a composite TV signal that includes a video signal as well as the BTSC format for the sound reproduction.
- the BTSC format is similar to FM stereo but has the ability to carry two additional audio channels.
- Left plus right (L+R) channel mono information 20 is transmitted in a way similar to stereo FM in order to ensure compatibility with monaural television receivers.
- a 15.734 KHz pilot signal 25 is used, instead of the FM stereo 19 KHz pilot signal, which allows the pilot signal 25 to be phase-locked to the horizontal line frequency.
- the stereo information is DBX encoded to aid in noise reduction.
- An SAP channel 40 is located at 5 times the pilot frequency.
- the SAP channel 40 may be used for second language or independent source program material.
- a professional audio channel (not shown) may be added at 6.5 times the pilot frequency 25 in order to accommodate additional voice or data.
- FIG. 2A is a schematic functional block diagram of the decoding method 100 used to decode the BTSC composite audio signal 10 of FIG. 1 in accordance with an embodiment of the present invention.
- the method 100 comprises analog-to-digital conversion 110 , digital amplitude compensation 115 , digital channel demodulation and filtering 120 , DBX decoding 130 , stereo re-matrixing 140 , and sample rate conversion 150 .
- the composite audio signal 10 is an analog baseband signal and is converted to a composite digital audio signal 11 in the analog-to-digital conversion step 110 .
- the analog-to-digital conversion step 110 operates at a clock rate of 20.25 MHz which is created by dividing down a master clock signal of 162 MHz by a factor of eight as shown in FIG. 2A .
- the composite digital audio signal 11 is output from the analog-to-digital conversion step 110 at a sample rate of 316.4 KHz and is presented to the digital amplitude compensation step 115 .
- the sample rate of 316.4 KHz is derived from the master clock signal by dividing down by a factor of 512.
- Step 115 the compensation of uneven frequency response, applies a second-order IIR filter to digitally compensate for amplitude unevenness in the composite digital audio signal due to an uneven frequency response of a previous IF demodulation stage that is not part of the decoding process described herein.
- the output of the digital amplitude compensation step 115 is a compensated composite audio signal 12 at a sample rate of 316.4 KHz.
- the compensated composite audio signal 12 is sent to the digital channel demodulation and filtering step 120 .
- Step 120 also operates at the sample rate of 316.4 KHz and effectively breaks up the compensated composite audio signal into the individual signal components including the left plus right (L+R) channel mono signal 20 , the 15.734 KHz pilot signal 25 , the left minus right (L ⁇ R) stereo signal 30 , and the SAP signal 40 .
- the SAP signal 40 is centered at five times the pilot signal 25 at a frequency of 78.67 KHz.
- step 120 first applies a band-pass FIR filter 121 to remove the L+R 20 and L ⁇ R 30 stereo channels and the professional channel if it is present in the composite signal.
- Step 120 then performs FM demodulation 122 by applying a Hilbert filter, a demodulation equation, and a low-pass filter to generate the FM demodulated SAP audio signal 123 .
- the resultant demodulated SAP audio signal 123 is at a sample rate of 158.2 KHz which is the master clock signal divided by 1024.
- the left minus right (L ⁇ R) stereo signal 30 is centered at twice the pilot signal frequency at 31.468 KHz and is a double sideband (DSB) suppressed carrier signal.
- the phase of the pilot signal 25 should be synchronized with the phase of the L ⁇ R DSB signal 30 to within three degrees in order to properly demodulate the signal.
- the phase of the L ⁇ R DSB signal 30 may be recovered by employing a digital phase-locked loop (DPLL) that is locked to the phase of the pilot signal 25 .
- DPLL digital phase-locked loop
- an eighth-order IIR band-pass filter 124 is applied to the digitized BTSC composite signal.
- the output of the band-pass filter 124 is then applied to a configuration 125 comprising a phase detector, a cosine look-up-table (LUT), and a loop filter as shown in FIG. 2B which also performs detection of the pilot signal 25 as part of the DPLL process.
- DSB demodulation is performed using the same cosine look-up-table (LUT) and a tenth-order elliptical IIR low-pass filter 126 also shown in FIG. 2B .
- the low-pass filter 126 has a pass-band ripple of ⁇ 0.1 dB at 13 KHz, 50 dB of attenuation at 15.734 KHz (the pilot signal frequency), and over 80 dB of attenuation above 19 KHz.
- the output is a demodulated version 127 of the left minus right (L ⁇ R) stereo signal 30 at a sample rate of 158.2 KHz as shown in FIG. 2A and FIG. 2B .
- Further details about demodulating the L ⁇ R DSB component 30 of the composite audio signal 10 may be found in the application entitled “System and Method of Performing Analog Multi-Channel Audio Signal Amplitude Correction” filed under docket number 13588US01 on the same day as the application herein (docket number 13578US01) was filed, and in the application “Pilot Tone Based Automatic Gain Control System and Method” filed under docket number 13589US01 on the same day as the application herein (docket number 13578US01) was filed.
- Step 120 is also used to demodulate the left plus right (L+R) channel mono signal 20 .
- the L+R signal 20 is first applied to the same tenth-order elliptical low-pass filter 126 having a pass-band ripple of ⁇ 0.1 dB at 13 KHz, 50 dB of attenuation at 15.734 KHz (the pilot signal frequency), and over 80 dB of attenuation above 19 KHz.
- the noise accompanying a received audio signal increases rapidly in the higher audio frequency range.
- the audio signal is pre-emphasized to raise the level of the higher audio frequencies relative to the lower audio frequencies.
- the received audio signal needs to be de-emphasized, yielding an overall flat audio frequency response while greatly reducing the effects of noise introduced by the transmission process.
- the output of the low-pass filter 126 in fed to a 75 micro-second de-emphasis digital filter 128 .
- the transfer function of the de-emphasis digital filter 128 is
- the resultant L+R demodulated audio signal 129 is at a sample rate of 31.64 KHz which is the master clock frequency of 162 MHz divided down by a factor of 5120. As shown in FIG. 2A , the demodulated L+R audio signal 129 may be fed to re-matrixing step 140 or to sample rate conversion step 150 .
- Both the left minus right (L ⁇ R) stereo channel 30 and the SAP channel 40 are originally DBX encoded on transmit to aid in noise reduction.
- DBX encoding is also known as signal companding.
- Signal companding is a technique used to reduce the effects of noise introduced by signal losses, circuit limitations, and interference during transmission of an audio signal.
- the audio signal to be transmitted is first dynamically compressed by a certain factor to reduce the overall dynamic range of the audio signal. Upon reception, the audio signal is expanded by a corresponding factor, thereby restoring the original dynamic range of the audio signal and reducing transmission noise.
- FIG. 3A is a schematic functional block diagram of a combination of digital filters 131 used to perform DBX decoding 130 in accordance with an embodiment of the present invention.
- a total of seven digital filters with transfer functions H 1 -H 7 ( 132 , 133 , 134 , 136 , 137 , 139 , and 141 ) are used as shown in FIG. 3A .
- the equations of the transfer functions H 1 -H 7 are shown in FIG. 4 in both analog form 160 and digital form 165 .
- the analog form 160 of the transfer functions H 1 -H 7 have been translated to the digital form 165 .
- the digital form 165 is implemented as shown in FIG. 3A .
- the unique combination of digital filters performs adaptive audio signal companding based on the frequency and magnitude of the incoming demodulated audio signal (e.g. SAP or L ⁇ R).
- DBX decoding 130 is done at a sample rate of 158.2 KHz, which is the master clock frequency of 162 MHz divided down by a factor of 1024.
- the output of the DBX decoding step 130 is a decoded audio signal 142 (e.g. SAP or L ⁇ R) at a sample rate of 31.64 KHz.
- a feature of the DBX decoding step 130 is the efficient implementation of the transfer function H 2 139 shown in FIG. 3A .
- Transfer function H 2 performs variable de-emphasis as a function of frequency and magnitude of the demodulated audio signal.
- a root mean square detector 135 is implemented as part of the DBX decoding step using transfer functions H 5 136 and H 7 137 and square root operation 138 ( FIG. 4 illustrates how the square root operation is performed).
- An output of the root mean square detector 135 is a coefficient “b” 144 which is input to transfer function H 2 and is a function of audio signal frequency and magnitude.
- the coefficient 147 A of transfer function H 2 is implemented as a look-up-table (LUT) 145 and a linear interpolator 146 as shown in FIG. 3B .
- the coefficient “b” 144 addresses the LUT 145 which then outputs the two nearest LUT data values corresponding to input “b”.
- the resolution of the LUT data values is designed to be coarse, thus minimizing the number of values that need to be stored in the LUT.
- the interpolator 146 then interpolates between the two output data values from the LUT 145 to generate an intermediate coefficient value 147 A having a finer resolution and more accurately representing the output of the LUT for the input “b”.
- the intermediate coefficient value 147 A is
- the intermediate coefficient value 147 A is sent to IIR coefficients generator 146 A.
- three IIR coefficients are generated based on the intermediate coefficient value 147 A and are sent to IIR filter 146 B.
- the three IIR coefficients are
- IIR filter 146 B then generates output value 147 that is sent to transfer function H 3 141 .
- the configuration of FIG. 3B effectively implements the transfer function equation 165 A for H 2 shown in FIG. 4 .
- the desired fine resolution of the output 147 of transfer function H 2 139 may be achieved without implementing a more complicated design requiring more memory and/or more computation.
- step 140 of the decoding method 100 the DBX decoded L ⁇ R audio signal 142 and the demodulated L+R audio signal 129 may be re-matrixed to form a left audio signal 148 and a right audio signal 149 at a sample rate of 31.64 KHz. Re-matrixing 140 is accomplished as
- re-matrixing 140 recovers the original stereo left 148 and right 149 audio signals.
- sampling rate conversion 150 is performed on the decoded SAP audio signal 142 , the demodulated mono audio signal (L+R) 129 , or the stereo left 148 and right 149 audio signals.
- Sampling rate conversion 150 is a process of translating the audio signal sampling rate of 31.64 KHz to a sampling rate including one of the standard audio output sampling rates of 32 KHz, 44.1 KHz, or 48 KHz in accordance with an embodiment of the present invention.
- An embodiment of the present invention accomplishes sampling rate conversion 150 by performing a combination of signal up-sampling, interpolation, and signal down-sampling.
- sampling rate conversion 150 A feature of one embodiment of the present invention with respect to sampling rate conversion 150 is that any of the resultant audio output signals (SAP out 151 , mono out 152 , left out 153 , right out 154 ) may be output at any one of the three standard audio output sampling rates listed above by using the same set of low-pass filter coefficients in the SRC conversion process 150 . Further details of an embodiment of sampling rate conversion may be found in the application entitled “System and Method of Performing Sample Rate Conversion” filed under docket number 13587US01 on the same day as the application herein (docket number 13578US01) was filed.
- FIG. 5 is a schematic block diagram of a decoding system 200 implemented on an ASIC chip and used to implement the decoding method 100 of FIG. 2A in accordance with an embodiment of the present invention.
- System 200 comprises various blocks implemented on an ASIC chip in accordance with an embodiment of the present invention.
- Block 210 is a sigma-delta analog-to-digital (A/D) conversion block operating on composite analog audio signal 10 and performing the function of step 110 in FIG. 2A to generate a low noise, high resolution composite digital audio signal 11 .
- Block 230 is a clock generation block generating clock signals of 20.25 MHz, 316.4 KHz, and buffer clock signals related to the standard output sampling rates from a master clock signal of 162 MHz. The clock signals are used in the multi-channel audio signal decoding process of FIG. 2A .
- Block 250 is a DSP processing block that performs many of the functions of the decoding process of FIG. 2 .
- Block 220 is an input buffer block connected between the A/D conversion block 210 and the DSP processing block 250 and is used to transfer composite digital audio signal data 11 into the DSP processing block 250 .
- a configuration register block 240 interfaces to DSP processing block 250 , input buffer block 220 , and A/D conversion block 210 to provide configuration data to the system 200 .
- Output buffer block 260 interfaces to DSP processing block 250 and clock generation block 230 to output standard audio output signals at standard audio output rates such as 32 KHz, 44.1 KHz, and 48 KHz in accordance with an embodiment of the present invention.
- DSP processing block 250 includes two port data RAM memory 251 for temporary storage of data.
- DSP processing block 250 also includes coefficient ROM/RAM memory 252 for storing sets of coefficients used in the digital multi-channel audio signal decoding process of FIG. 2A .
- instruction RAM memory 253 stores a set of instructions 300 to be executed by the DSP processing block 250 (see FIG. 7 ).
- Instruction decoder 254 interprets the set of instructions 300 in instruction RAM memory 253 .
- the set of instructions 300 include those defined in FIG. 7 and are used to perform the functions of FIG. 2A .
- DSP processing block 250 includes a five-stage pipelined data path 255 to execute the set of instructions 300 of FIG. 7 .
- FIG. 6 shows the five-stage pipelined data path 255 in accordance with an embodiment of the present invention.
- the 5-stages include memory address calculation stage 256 , memory data fetch stage 257 , multiplication stage 258 , accumulation/mantissa-generation/signal-shifter stage 259 , and registers/memory-write stage 261 .
- the five-stage pipelined data path 255 along with the set of instructions 300 are used to execute the decoding functions of FIG. 2A including digital amplitude compensation 1 . 15 , digital channel demodulation and filtering 120 , DBX decoding 130 , re-matrixing 140 , and sampling rate conversion 150 .
- instruction 5 ( 301 ), 20-bit first-order IIR filtering, may be performed by the five-stage pipelined data path 255 in no more than three clock cycles.
- instruction 6 ( 302 ), 20-bit second-order IIR filtering, may be performed in no more than five clock cycles.
- FIG. 5 may be combined or separated according to various embodiments of the present invention within the ASIC chip or may be separated and implemented over more than one chip.
- certain embodiments of the present invention use several stages of digital signal processing where each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage.
- certain embodiments of the present invention afford an approach to achieve efficient, low cost, low power, digital multi-channel audio signal decoding of BTSC audio signals in the digital domain.
Abstract
Description
- The present application is a continuation of U.S. patent application Ser. No. 11/426,836, filed Jun. 27, 2006 (now U.S. Pat. No. 7,912,153), which is a continuation of U.S. patent application Ser. No. 10/083,052, filed Feb. 26, 2002 (now U.S. Pat. No. 7,079,657), and is related to the following applications: U.S. application Ser. No. 10/083,076 (now U.S. Pat. No. 7,006,806) (docket number 13586US01), U.S. application Ser. No. 10/082,950 (docket number 13587US01), U.S. application Ser. No. 10/083,203 (now U.S. Pat. No. 6,859,238) (docket number 13588US01), and U.S. application Ser. No. 10/083,201 (now U.S. Pat. No. 6,832,078) (docket number 13589US01), all of said related applications having a filing date of Feb. 26, 2002.
- [Not Applicable]
- [Not Applicable]
- Certain embodiments of the present invention relate to the processing of multi-channel television signals. More specifically, certain embodiments relate to a system and method for digitally decoding BTCS (Broadcast Television System Committee) audio signals.
- During the 1980's, the FCC adopted the BTSC format as a standard for multi-channel television sound (MTS). Typically, the BTSC format is used with a composite TV signal that includes a video signal as well as the BTSC format for the sound reproduction.
- The BTSC format is similar to FM stereo but has the ability to carry two additional audio channels. Left plus right (L+R) channel mono information is transmitted in a way similar to stereo FM in order to ensure compatibility with monaural television receivers. A 15.734 KHz pilot signal is used, instead of the FM stereo 19 KHz pilot signal, which allows the pilot signal to be phase-locked to the horizontal line frequency. A double sideband-suppressed carrier at twice the frequency of the pilot transmits the left minus right (L−R) stereo information. The stereo information is DBX encoded to aid in noise reduction. An SAP channel is located at 5 times the pilot frequency. The SAP channel may be used for second language or independent source program material. A professional audio channel may be added at 6.5 times the pilot frequency in order to accommodate additional voice or data.
- Stereo tuners and demodulator units capable of decoding the BTSC format have been on the market for some time. The front end of the units typically includes analog components or integrated circuit chips. Traditionally, BTSC decoding has been done in the analog domain requiring larger, more expensive implementations that consume a significant amount of power. Previous digital implementations may not be optimized, requiring many clock cycles to perform various processing functions.
- It is desirable to perform BTSC decoding in the digital domain on a block of an ASIC chip such that the implementation is optimized for reduced complexity and cost. By reducing the complexity, fewer clock cycles are required for processing, and power consumption is also reduced.
- Further limitations and disadvantages of conventional and traditional approaches will become apparent to one of skill in the art, through comparison of such systems with embodiments of the present invention as set forth in the remainder of the present application with reference to the drawings.
- A need exists for an approach to perform efficient multi-channel audio signal decoding in the digital domain by reducing the complexity of the hardware required, therefore reducing cost and power consumption.
- An embodiment of the present invention provides efficient, low cost digital multi-channel audio signal decoding of BTSC audio signals in the digital domain. In such an environment, several stages of digital signal processing are used where each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage. Efficient pipelined processing is used to execute the various processing functions in order to reduce clock cycles and addressing to memory.
- A method is provided for performing digital multi-channel decoding of a DBX-encoded composite audio signal. Each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage. Analog-to-digital conversion of the composite audio signal is performed first to generate a composite digital audio signal. After analog-to-digital conversion, all signal processing may be performed in the digital domain. The composite digital audio signal is digitally filtered to compensate for uneven frequency response caused by previous stages of processing, including IF demodulation. Digital channel demodulation and filtering are performed to isolate single channels of the composite digital audio signal such as SAP, L−R, and L+R channels. SAP and L−R channels are DBX decoded resulting in corresponding decoded signals using a unique combination of digital filters that are an efficient translation of a corresponding combination of analog filters. The decoded L−R channel and the L+R channel are re-matrixed to form left and right stereo signals. Any of the SAP signal, left and right stereo signals, and L+R channel signal may be sample rate converted and output at a standard audio output rate.
- A system is provided on an ASIC chip for performing digital multi-channel audio signal decoding. The system comprises a sigma-delta analog-to-digital (A/D) conversion block operating on a composite analog audio signal to generate a composite digital audio signal, a clock generation block generating a master clock signal and other clock signals used in the multi-channel audio signal decoding process, and a DSP processing block including a five-stage pipelined data path performing certain digital multi-channel audio signal processing functions in response to a set of instructions. The system further includes an input buffer block connected between the sigma-delta A/D conversion block and the DSP processing block to transfer the composite digital audio signal to the DSP processing block, a configuration register block interfacing to the DSP processing block, the input buffer block, and the sigma-delta A/D conversion block, and an output buffer block interfacing to the DSP processing block and the clock generation block to output standard audio output signals at standard audio output rates. The five-stage pipelined data path comprises a memory address calculation stage, a memory data fetch stage, a multiplication stage, an accumulation/mantissa-generation/signal-shifter stage, and a registers/memory-write stage.
- Certain embodiments of the present invention afford an approach to achieve efficient, low cost digital multi-channel audio signal decoding of BTSC audio signals in the digital domain. Certain embodiments of the present invention use several stages of digital signal processing where each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage.
-
FIG. 1 is an illustration of the various components of a composite audio signal to be decoded in accordance with an embodiment of the present invention. -
FIG. 2A is a schematic functional block diagram of the decoding method used to decode the composite audio signal ofFIG. 1 in accordance with an embodiment of the present invention. -
FIG. 2B is a schematic functional block diagram of pilot signal detection and DSB demodulation performed in the method ofFIG. 2A in accordance with an embodiment of the present invention. -
FIG. 3A is a schematic functional block diagram of a combination of digital filter transfer functions used to perform DBX decoding in accordance with an embodiment of the present invention. -
FIG. 3B is a schematic functional block diagram of a transfer function ofFIG. 3A in accordance with an embodiment of the present invention. -
FIG. 4 illustrates the translated analog and digital transfer function equations corresponding to the DBX decoding performed inFIG. 3A in accordance with an embodiment of the present invention. -
FIG. 5 is a schematic block diagram of a decoding system implemented on an ASIC chip and used to implement the decoding method ofFIG. 2A in accordance with an embodiment of the present invention. -
FIG. 6 is a flowchart illustration of the data path processing performed by the pipelined decoding system ofFIG. 5 in accordance with an embodiment of the present invention. -
FIG. 7 is a table of instructions that may be implemented by the data path processing ofFIG. 6 in accordance with an embodiment of the present invention. -
FIG. 1 is an illustration of the various components of a BTSCcomposite audio signal 10 to be decoded in accordance with an embodiment of the present invention. During the 1980's, the FCC adopted the BTSC format as a standard for multi-channel television sound (MTS). Typically, the BTSC format is used with a composite TV signal that includes a video signal as well as the BTSC format for the sound reproduction. - The BTSC format is similar to FM stereo but has the ability to carry two additional audio channels. Left plus right (L+R)
channel mono information 20 is transmitted in a way similar to stereo FM in order to ensure compatibility with monaural television receivers. A 15.734KHz pilot signal 25 is used, instead of the FM stereo 19 KHz pilot signal, which allows thepilot signal 25 to be phase-locked to the horizontal line frequency. A double sideband-suppressed carrier, at twice the frequency of the pilot, transmits the left minus right (L−R)stereo information 30. The stereo information is DBX encoded to aid in noise reduction. AnSAP channel 40 is located at 5 times the pilot frequency. TheSAP channel 40 may be used for second language or independent source program material. A professional audio channel (not shown) may be added at 6.5 times thepilot frequency 25 in order to accommodate additional voice or data. -
FIG. 2A is a schematic functional block diagram of thedecoding method 100 used to decode the BTSCcomposite audio signal 10 ofFIG. 1 in accordance with an embodiment of the present invention. Themethod 100 comprises analog-to-digital conversion 110,digital amplitude compensation 115, digital channel demodulation andfiltering 120,DBX decoding 130,stereo re-matrixing 140, andsample rate conversion 150. - The
composite audio signal 10 is an analog baseband signal and is converted to a compositedigital audio signal 11 in the analog-to-digital conversion step 110. As a result, subsequent processing may be performed in the digital domain. The analog-to-digital conversion step 110 operates at a clock rate of 20.25 MHz which is created by dividing down a master clock signal of 162 MHz by a factor of eight as shown inFIG. 2A . The compositedigital audio signal 11 is output from the analog-to-digital conversion step 110 at a sample rate of 316.4 KHz and is presented to the digitalamplitude compensation step 115. The sample rate of 316.4 KHz is derived from the master clock signal by dividing down by a factor of 512. -
Step 115, the compensation of uneven frequency response, applies a second-order IIR filter to digitally compensate for amplitude unevenness in the composite digital audio signal due to an uneven frequency response of a previous IF demodulation stage that is not part of the decoding process described herein. The output of the digitalamplitude compensation step 115 is a compensatedcomposite audio signal 12 at a sample rate of 316.4 KHz. - The compensated
composite audio signal 12 is sent to the digital channel demodulation andfiltering step 120. Step 120 also operates at the sample rate of 316.4 KHz and effectively breaks up the compensated composite audio signal into the individual signal components including the left plus right (L+R)channel mono signal 20, the 15.734 KHzpilot signal 25, the left minus right (L−R)stereo signal 30, and theSAP signal 40. - The
SAP signal 40 is centered at five times thepilot signal 25 at a frequency of 78.67 KHz. In order to demodulate this part of the composite audio signal, step 120 first applies a band-pass FIR filter 121 to remove the L+R 20 and L−R 30 stereo channels and the professional channel if it is present in the composite signal. Step 120 then performsFM demodulation 122 by applying a Hilbert filter, a demodulation equation, and a low-pass filter to generate the FM demodulatedSAP audio signal 123. The resultant demodulatedSAP audio signal 123 is at a sample rate of 158.2 KHz which is the master clock signal divided by 1024. Further details about demodulating theSAP component 40 of thecomposite audio signal 10 may be found in the application entitled “System and Method for SAP FM Demodulation” filed under docket number 13586US01 on the same day as the application herein (docket number 13578US01) was filed. - The left minus right (L−R)
stereo signal 30 is centered at twice the pilot signal frequency at 31.468 KHz and is a double sideband (DSB) suppressed carrier signal. According toFCC OET 6, the phase of thepilot signal 25 should be synchronized with the phase of the L−R DSB signal 30 to within three degrees in order to properly demodulate the signal. The phase of the L−R DSB signal 30 may be recovered by employing a digital phase-locked loop (DPLL) that is locked to the phase of thepilot signal 25. Referring toFIG. 2B , to perform the DPLL function, an eighth-order IIR band-pass filter 124 is applied to the digitized BTSC composite signal. The output of the band-pass filter 124 is then applied to aconfiguration 125 comprising a phase detector, a cosine look-up-table (LUT), and a loop filter as shown inFIG. 2B which also performs detection of thepilot signal 25 as part of the DPLL process. Finally DSB demodulation is performed using the same cosine look-up-table (LUT) and a tenth-order elliptical IIR low-pass filter 126 also shown inFIG. 2B . The low-pass filter 126 has a pass-band ripple of −0.1 dB at 13 KHz, 50 dB of attenuation at 15.734 KHz (the pilot signal frequency), and over 80 dB of attenuation above 19 KHz. The output is ademodulated version 127 of the left minus right (L−R)stereo signal 30 at a sample rate of 158.2 KHz as shown inFIG. 2A andFIG. 2B . Further details about demodulating the L−R DSB component 30 of thecomposite audio signal 10 may be found in the application entitled “System and Method of Performing Analog Multi-Channel Audio Signal Amplitude Correction” filed under docket number 13588US01 on the same day as the application herein (docket number 13578US01) was filed, and in the application “Pilot Tone Based Automatic Gain Control System and Method” filed under docket number 13589US01 on the same day as the application herein (docket number 13578US01) was filed. - Step 120 is also used to demodulate the left plus right (L+R)
channel mono signal 20. The L+R signal 20 is first applied to the same tenth-order elliptical low-pass filter 126 having a pass-band ripple of −0.1 dB at 13 KHz, 50 dB of attenuation at 15.734 KHz (the pilot signal frequency), and over 80 dB of attenuation above 19 KHz. - In FM systems, the noise accompanying a received audio signal increases rapidly in the higher audio frequency range. To offset the effect, at the transmitter the audio signal is pre-emphasized to raise the level of the higher audio frequencies relative to the lower audio frequencies. As a result, the received audio signal needs to be de-emphasized, yielding an overall flat audio frequency response while greatly reducing the effects of noise introduced by the transmission process.
- To accomplish the de-emphasis of the L+
R signal 20, the output of the low-pass filter 126 in fed to a 75 micro-second de-emphasisdigital filter 128. In an embodiment of the present invention, the transfer function of the de-emphasisdigital filter 128 is -
- The resultant L+R demodulated
audio signal 129 is at a sample rate of 31.64 KHz which is the master clock frequency of 162 MHz divided down by a factor of 5120. As shown inFIG. 2A , the demodulated L+R audio signal 129 may be fed tore-matrixing step 140 or to samplerate conversion step 150. - Both the left minus right (L−R)
stereo channel 30 and theSAP channel 40 are originally DBX encoded on transmit to aid in noise reduction. DBX encoding is also known as signal companding. Signal companding is a technique used to reduce the effects of noise introduced by signal losses, circuit limitations, and interference during transmission of an audio signal. The audio signal to be transmitted is first dynamically compressed by a certain factor to reduce the overall dynamic range of the audio signal. Upon reception, the audio signal is expanded by a corresponding factor, thereby restoring the original dynamic range of the audio signal and reducing transmission noise. - Therefore, the left minus right (L−R) stereo channel and the
SAP channel 40 must be DBX decoded after demodulation andfiltering step 120. DBX decoding is accomplished instep 130 as shown inFIG. 2A .FIG. 3A is a schematic functional block diagram of a combination ofdigital filters 131 used to performDBX decoding 130 in accordance with an embodiment of the present invention. A total of seven digital filters with transfer functions H1-H7 (132, 133, 134, 136, 137, 139, and 141) are used as shown inFIG. 3A . The equations of the transfer functions H1-H7 are shown inFIG. 4 in bothanalog form 160 anddigital form 165. In an embodiment of the present invention, theanalog form 160 of the transfer functions H1-H7 have been translated to thedigital form 165. Thedigital form 165 is implemented as shown inFIG. 3A . The unique combination of digital filters performs adaptive audio signal companding based on the frequency and magnitude of the incoming demodulated audio signal (e.g. SAP or L−R).DBX decoding 130 is done at a sample rate of 158.2 KHz, which is the master clock frequency of 162 MHz divided down by a factor of 1024. The output of theDBX decoding step 130 is a decoded audio signal 142 (e.g. SAP or L−R) at a sample rate of 31.64 KHz. - A feature of the
DBX decoding step 130 is the efficient implementation of thetransfer function H2 139 shown inFIG. 3A . Transfer function H2 performs variable de-emphasis as a function of frequency and magnitude of the demodulated audio signal. A root meansquare detector 135 is implemented as part of the DBX decoding step usingtransfer functions H5 136 andH7 137 and square root operation 138 (FIG. 4 illustrates how the square root operation is performed). An output of the root meansquare detector 135 is a coefficient “b” 144 which is input to transfer function H2 and is a function of audio signal frequency and magnitude. - For implementation and computation efficiency, the
coefficient 147A of transfer function H2 is implemented as a look-up-table (LUT) 145 and alinear interpolator 146 as shown inFIG. 3B . The coefficient “b” 144 addresses theLUT 145 which then outputs the two nearest LUT data values corresponding to input “b”. The resolution of the LUT data values is designed to be coarse, thus minimizing the number of values that need to be stored in the LUT. Theinterpolator 146 then interpolates between the two output data values from theLUT 145 to generate anintermediate coefficient value 147A having a finer resolution and more accurately representing the output of the LUT for the input “b”. In an embodiment of the present invention, theintermediate coefficient value 147A is -
1/(3b/103+1) [2] - The
intermediate coefficient value 147A is sent toIIR coefficients generator 146A. In one embodiment of the present invention, three IIR coefficients are generated based on theintermediate coefficient value 147A and are sent toIIR filter 146B. The three IIR coefficients are -
a(1)=(b/103+101/103)/(3b/103+1) [3] -
b(0)=(b+3/103)/(3b/103+1) [4] -
b(1)=(101b/103+1/103)/(3b/103+1) [5] -
IIR filter 146B then generatesoutput value 147 that is sent totransfer function H3 141. The configuration ofFIG. 3B effectively implements thetransfer function equation 165A for H2 shown inFIG. 4 . As a result, the desired fine resolution of theoutput 147 oftransfer function H2 139 may be achieved without implementing a more complicated design requiring more memory and/or more computation. - In
step 140 of thedecoding method 100, the DBX decoded L−R audio signal 142 and the demodulated L+R audio signal 129 may be re-matrixed to form aleft audio signal 148 and aright audio signal 149 at a sample rate of 31.64 KHz.Re-matrixing 140 is accomplished as -
left=(S+D)/2 [6] -
and -
right=(S−D)/2 [7] - where S=L+R and D=L−R. Therefore, re-matrixing 140 recovers the original stereo left 148 and right 149 audio signals.
- In
step 150, sampling rate conversion (SRC) is performed on the decodedSAP audio signal 142, the demodulated mono audio signal (L+R) 129, or the stereo left 148 and right 149 audio signals.Sampling rate conversion 150 is a process of translating the audio signal sampling rate of 31.64 KHz to a sampling rate including one of the standard audio output sampling rates of 32 KHz, 44.1 KHz, or 48 KHz in accordance with an embodiment of the present invention. An embodiment of the present invention accomplishessampling rate conversion 150 by performing a combination of signal up-sampling, interpolation, and signal down-sampling. - A feature of one embodiment of the present invention with respect to
sampling rate conversion 150 is that any of the resultant audio output signals (SAP out 151, mono out 152, left out 153, right out 154) may be output at any one of the three standard audio output sampling rates listed above by using the same set of low-pass filter coefficients in theSRC conversion process 150. Further details of an embodiment of sampling rate conversion may be found in the application entitled “System and Method of Performing Sample Rate Conversion” filed under docket number 13587US01 on the same day as the application herein (docket number 13578US01) was filed. -
FIG. 5 is a schematic block diagram of adecoding system 200 implemented on an ASIC chip and used to implement thedecoding method 100 ofFIG. 2A in accordance with an embodiment of the present invention. -
System 200 comprises various blocks implemented on an ASIC chip in accordance with an embodiment of the present invention.Block 210 is a sigma-delta analog-to-digital (A/D) conversion block operating on compositeanalog audio signal 10 and performing the function ofstep 110 inFIG. 2A to generate a low noise, high resolution compositedigital audio signal 11.Block 230 is a clock generation block generating clock signals of 20.25 MHz, 316.4 KHz, and buffer clock signals related to the standard output sampling rates from a master clock signal of 162 MHz. The clock signals are used in the multi-channel audio signal decoding process ofFIG. 2A .Block 250 is a DSP processing block that performs many of the functions of the decoding process ofFIG. 2 .Block 220 is an input buffer block connected between the A/D conversion block 210 and theDSP processing block 250 and is used to transfer composite digitalaudio signal data 11 into theDSP processing block 250. Aconfiguration register block 240 interfaces toDSP processing block 250,input buffer block 220, and A/D conversion block 210 to provide configuration data to thesystem 200.Output buffer block 260 interfaces toDSP processing block 250 andclock generation block 230 to output standard audio output signals at standard audio output rates such as 32 KHz, 44.1 KHz, and 48 KHz in accordance with an embodiment of the present invention. - In accordance with an embodiment of the present invention,
DSP processing block 250 includes two portdata RAM memory 251 for temporary storage of data.DSP processing block 250 also includes coefficient ROM/RAM memory 252 for storing sets of coefficients used in the digital multi-channel audio signal decoding process ofFIG. 2A . Also included inDSP processing block 250 areinstruction RAM memory 253 andinstruction decoder 254.Instruction RAM memory 253 stores a set ofinstructions 300 to be executed by the DSP processing block 250 (seeFIG. 7 ).Instruction decoder 254 interprets the set ofinstructions 300 ininstruction RAM memory 253. In accordance with an embodiment of the present invention, the set ofinstructions 300 include those defined inFIG. 7 and are used to perform the functions ofFIG. 2A . Finally,DSP processing block 250 includes a five-stage pipelineddata path 255 to execute the set ofinstructions 300 ofFIG. 7 . -
FIG. 6 shows the five-stage pipelineddata path 255 in accordance with an embodiment of the present invention. The 5-stages include memoryaddress calculation stage 256, memory data fetchstage 257,multiplication stage 258, accumulation/mantissa-generation/signal-shifter stage 259, and registers/memory-write stage 261. - The five-stage pipelined
data path 255 along with the set ofinstructions 300 are used to execute the decoding functions ofFIG. 2A including digital amplitude compensation 1.15, digital channel demodulation andfiltering 120,DBX decoding 130, re-matrixing 140, andsampling rate conversion 150. - A feature of a preferred embodiment of the present invention is that instruction 5 (301), 20-bit first-order IIR filtering, may be performed by the five-stage pipelined
data path 255 in no more than three clock cycles. Another feature of a preferred embodiment of the present invention is that instruction 6 (302), 20-bit second-order IIR filtering, may be performed in no more than five clock cycles. - The various blocks illustrated in
FIG. 5 may be combined or separated according to various embodiments of the present invention within the ASIC chip or may be separated and implemented over more than one chip. - In summary, certain embodiments of the present invention use several stages of digital signal processing where each subsequent stage of the digital multi-channel decoding process is performed at the lowest sampling rate that yields acceptable performance for that stage. As a result, certain embodiments of the present invention afford an approach to achieve efficient, low cost, low power, digital multi-channel audio signal decoding of BTSC audio signals in the digital domain.
- While the invention has been described with reference to certain embodiments, it will be understood by those skilled in the art that various changes may be made and equivalents may be substituted without departing from the scope of the invention. In addition, many modifications may be made to adapt a particular situation or material to the teachings of the invention without departing from its scope. Therefore, it is intended that the invention not be limited to the particular embodiment disclosed, but that the invention will include all embodiments falling within the scope of the appended claims.
Claims (11)
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US13/069,090 US20110211658A1 (en) | 2002-02-26 | 2011-03-22 | System and method of performing digital multi-channel audio signal decoding |
Applications Claiming Priority (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US10/083,052 US7079657B2 (en) | 2002-02-26 | 2002-02-26 | System and method of performing digital multi-channel audio signal decoding |
US11/426,836 US7912153B2 (en) | 2002-02-26 | 2006-06-27 | System and method of performing digital multi-channel audio signal decoding |
US13/069,090 US20110211658A1 (en) | 2002-02-26 | 2011-03-22 | System and method of performing digital multi-channel audio signal decoding |
Related Parent Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US11/426,836 Continuation US7912153B2 (en) | 2002-02-26 | 2006-06-27 | System and method of performing digital multi-channel audio signal decoding |
Publications (1)
Publication Number | Publication Date |
---|---|
US20110211658A1 true US20110211658A1 (en) | 2011-09-01 |
Family
ID=27753226
Family Applications (3)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US10/083,052 Expired - Fee Related US7079657B2 (en) | 2002-02-26 | 2002-02-26 | System and method of performing digital multi-channel audio signal decoding |
US11/426,836 Expired - Fee Related US7912153B2 (en) | 2002-02-26 | 2006-06-27 | System and method of performing digital multi-channel audio signal decoding |
US13/069,090 Abandoned US20110211658A1 (en) | 2002-02-26 | 2011-03-22 | System and method of performing digital multi-channel audio signal decoding |
Family Applications Before (2)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US10/083,052 Expired - Fee Related US7079657B2 (en) | 2002-02-26 | 2002-02-26 | System and method of performing digital multi-channel audio signal decoding |
US11/426,836 Expired - Fee Related US7912153B2 (en) | 2002-02-26 | 2006-06-27 | System and method of performing digital multi-channel audio signal decoding |
Country Status (1)
Country | Link |
---|---|
US (3) | US7079657B2 (en) |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP2608409A1 (en) | 2011-12-20 | 2013-06-26 | Televic Conference NV | Multichannel sample rate converter |
CN107888206A (en) * | 2017-11-09 | 2018-04-06 | 中国电子科技集团公司第二十九研究所 | A kind of AM voice signals demodulating data Audio recovery method and recording method |
Families Citing this family (28)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7397850B2 (en) | 1999-02-18 | 2008-07-08 | Easley Mathew F | Reciprocal index lookup for BTSC compatible coefficients |
WO2004100604A1 (en) * | 2000-02-18 | 2004-11-18 | Arris International, Inc. | Reciprocal index lookup for btsc compatible coefficients |
US7079657B2 (en) * | 2002-02-26 | 2006-07-18 | Broadcom Corporation | System and method of performing digital multi-channel audio signal decoding |
MXPA05005353A (en) * | 2002-11-19 | 2005-10-05 | Cable Electronics Inc | Digitally decoding an mts signal. |
US20050027771A1 (en) * | 2003-07-30 | 2005-02-03 | Broadcom Corporation | System and method for approximating division |
US7489362B2 (en) | 2003-03-04 | 2009-02-10 | Broadcom Corporation | Television functionality on a chip |
US20050036357A1 (en) * | 2003-08-15 | 2005-02-17 | Broadcom Corporation | Digital signal processor having a programmable address generator, and applications thereof |
US7463310B2 (en) * | 2003-08-14 | 2008-12-09 | Broadcom Corporation | BTSC pilot signal lock |
WO2005048598A1 (en) * | 2003-11-07 | 2005-05-26 | Thomson Licensing | Recording mono primary and sap or primary stereo |
US7406302B1 (en) | 2003-12-15 | 2008-07-29 | Marvell International, Inc. | Digital FM stereo receiver architecture |
MXPA06010869A (en) * | 2004-03-24 | 2007-01-19 | That Corp | Configurable filter for processing television audio signals. |
EP1787409A4 (en) * | 2004-08-17 | 2010-10-20 | That Corp | Configurable recursive digital filter for processing television audio signals |
US7890563B2 (en) * | 2005-03-15 | 2011-02-15 | Analog Devices, Inc. | Multi-channel sample rate conversion method |
US7468763B2 (en) * | 2005-08-09 | 2008-12-23 | Texas Instruments Incorporated | Method and apparatus for digital MTS receiver |
US7453288B2 (en) * | 2006-02-16 | 2008-11-18 | Sigmatel, Inc. | Clock translator and parallel to serial converter |
US7856464B2 (en) * | 2006-02-16 | 2010-12-21 | Sigmatel, Inc. | Decimation filter |
US7724861B2 (en) * | 2006-03-22 | 2010-05-25 | Sigmatel, Inc. | Sample rate converter |
US7792220B2 (en) * | 2006-12-19 | 2010-09-07 | Sigmatel, Inc. | Demodulator system and method |
US7831001B2 (en) * | 2006-12-19 | 2010-11-09 | Sigmatel, Inc. | Digital audio processing system and method |
US7729461B2 (en) * | 2006-12-22 | 2010-06-01 | Sigmatel, Inc. | System and method of signal processing |
US8094836B2 (en) * | 2008-04-08 | 2012-01-10 | Mediatek Inc. | Multi-channel decoding systems capable of reducing noise and methods thereof |
US8964991B2 (en) * | 2008-06-17 | 2015-02-24 | Himax Tehnologies Limted | Method for processing an input composite signal and signal processing apparatus thereof |
US8626516B2 (en) * | 2009-02-09 | 2014-01-07 | Broadcom Corporation | Method and system for dynamic range control in an audio processing system |
KR101599884B1 (en) * | 2009-08-18 | 2016-03-04 | 삼성전자주식회사 | Method and apparatus for decoding multi-channel audio |
US9397683B2 (en) * | 2014-08-05 | 2016-07-19 | Intel Corporation | Reduced digital audio sampling rates in digital audio processing chain |
CN105047114A (en) * | 2015-08-27 | 2015-11-11 | 王国运 | Tourism and conference broadcasting audio guide based on digital RF frequency-modulation technology |
TWI743800B (en) | 2020-05-22 | 2021-10-21 | 瑞昱半導體股份有限公司 | Circuitry and method for detecting audio standard of sound intermediate frequency signal |
CN113747144A (en) * | 2020-05-28 | 2021-12-03 | 瑞昱半导体股份有限公司 | Circuit and method for detecting system of sound intermediate frequency signal |
Citations (64)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4486897A (en) * | 1982-02-09 | 1984-12-04 | Sony Corporation | Television receiver for demodulating a two-language stereo broadcast signal |
US4506228A (en) * | 1981-09-26 | 1985-03-19 | Robert Bosch Gmbh | Digital FM detector |
US4626892A (en) * | 1984-03-05 | 1986-12-02 | Rca Corporation | Television system with menu like function control selection |
US4628539A (en) * | 1985-02-25 | 1986-12-09 | Rca Corporation | Muting circuit |
US4704726A (en) * | 1984-03-30 | 1987-11-03 | Rca Corporation | Filter arrangement for an audio companding system |
US4716589A (en) * | 1984-11-26 | 1987-12-29 | Nec Corporation | Multivoice signal switching circuit |
US4747140A (en) * | 1986-12-24 | 1988-05-24 | Rca Corporation | Low distortion filters for separating frequency or phase modulated signals from composite signals |
US4803700A (en) * | 1985-06-12 | 1989-02-07 | U.S. Philips Corp. | Method of, and demodulator for, digitally demodulating an SSB signal |
US4862099A (en) * | 1987-08-18 | 1989-08-29 | Mitsubishi Denki Kabushiki Kaisha | Digital FM demodulator with distortion correction |
US5091957A (en) * | 1990-04-18 | 1992-02-25 | Thomson Consumer Electronics, Inc. | Wideband expander for stereo and SAP signals |
US5149902A (en) * | 1989-12-07 | 1992-09-22 | Kabushiki Kaisha Kawai Gakki Seisakusho | Electronic musical instrument using filters for timbre control |
US5151926A (en) * | 1991-05-21 | 1992-09-29 | General Electric Company | Sample timing and carrier frequency estimation circuit for sine-cosine detectors |
US5250748A (en) * | 1986-12-30 | 1993-10-05 | Yamaha Corporation | Tone signal generation device employing a digital filter |
US5373562A (en) * | 1992-08-28 | 1994-12-13 | Thomson Consumer Electronics, Inc. | Signal processor for sterophonic signals |
US5404405A (en) * | 1993-08-05 | 1995-04-04 | Hughes Aircraft Company | FM stereo decoder and method using digital signal processing |
US5440269A (en) * | 1993-09-08 | 1995-08-08 | Samsung Electronics Co., Ltd. | Digital FM demodulator having an address circuit for a lookup table |
US5559513A (en) * | 1993-08-06 | 1996-09-24 | Deutsche Thomson-Brandt Gmbh | Digital sampling rate converter |
US5614862A (en) * | 1995-10-27 | 1997-03-25 | Icom Incorporated | Digital demodulator for a frequency modulated signal and an amplitude modulated signal |
US5903482A (en) * | 1997-06-20 | 1999-05-11 | Pioneer Electronic Corp. | Sampling frequency converting system and a method thereof |
US5907295A (en) * | 1997-08-04 | 1999-05-25 | Neomagic Corp. | Audio sample-rate conversion using a linear-interpolation stage with a multi-tap low-pass filter requiring reduced coefficient storage |
US6037993A (en) * | 1997-03-17 | 2000-03-14 | Antec Corporation | Digital BTSC compander system |
US6118879A (en) * | 1996-06-07 | 2000-09-12 | That Corporation | BTSC encoder |
US6122380A (en) * | 1997-12-01 | 2000-09-19 | Sony Corporation | Apparatus and method of providing stereo television audio signals |
US6192086B1 (en) * | 1999-01-14 | 2001-02-20 | Antec Corporation | Digital sub-systems and building blocks for a mostly digital low-cost BTSC compatible encoder |
US6208671B1 (en) * | 1998-01-20 | 2001-03-27 | Cirrus Logic, Inc. | Asynchronous sample rate converter |
US6259482B1 (en) * | 1998-03-11 | 2001-07-10 | Matthew F. Easley | Digital BTSC compander system |
US6281813B1 (en) * | 1999-07-09 | 2001-08-28 | Micronas Gmbh | Circuit for decoding an analog audio signal |
US6295362B1 (en) * | 1998-01-20 | 2001-09-25 | General Instrument Corporation | Direct digital synthesis of FM signals |
US6356598B1 (en) * | 1998-08-26 | 2002-03-12 | Thomson Licensing S.A. | Demodulator for an HDTV receiver |
US6442758B1 (en) * | 1999-09-24 | 2002-08-27 | Convedia Corporation | Multimedia conferencing system having a central processing hub for processing video and audio data for remote users |
US20020140853A1 (en) * | 2001-02-20 | 2002-10-03 | Seungjoon Yang | Sampling rate conversion apparatus and method thereof |
US6476878B1 (en) * | 1998-10-21 | 2002-11-05 | Scientific-Atlanta, Inc. | Method and apparatus for audio signal processing |
US20030018472A1 (en) * | 1998-01-08 | 2003-01-23 | Yehuda Hershkovits | Vocoder-based voice recognizer |
US6512555B1 (en) * | 1994-05-04 | 2003-01-28 | Samsung Electronics Co., Ltd. | Radio receiver for vestigal-sideband amplitude-modulation digital television signals |
US6535608B1 (en) * | 1999-05-24 | 2003-03-18 | Sanyo Electric Co., Ltd. | Stereo broadcasting receiving device |
US6542203B1 (en) * | 1998-11-12 | 2003-04-01 | Sony United Kingdom Limited | Digital receiver for receiving and demodulating a plurality of digital signals and method thereof |
US6552753B1 (en) * | 2000-10-19 | 2003-04-22 | Ilya Zhurbinskiy | Method and apparatus for maintaining uniform sound volume for televisions and other systems |
US20030087618A1 (en) * | 2001-11-08 | 2003-05-08 | Junsong Li | Digital FM stereo decoder and method of operation |
US20030091194A1 (en) * | 1999-12-08 | 2003-05-15 | Bodo Teichmann | Method and device for processing a stereo audio signal |
US6584145B1 (en) * | 1999-06-02 | 2003-06-24 | Level One Communications, Inc. | Sample rate converter |
US6608902B1 (en) * | 1998-02-07 | 2003-08-19 | Sigmatel, Inc. | Stereo signal separation circuit and application thereof |
US6611571B1 (en) * | 1998-06-16 | 2003-08-26 | Icom Incorporated | Apparatus and method for demodulating an angle-modulated signal |
US20030162517A1 (en) * | 2002-02-26 | 2003-08-28 | Wu David Chaohua | Scaling adjustment using pilot signal |
US20030161477A1 (en) * | 2002-02-26 | 2003-08-28 | Wu David Chaohua | System and method of performing digital multi-channel audio signal decoding |
US20030160905A1 (en) * | 2002-02-26 | 2003-08-28 | Wu David Chaohua | Scaling adjustment to enhance stereo separation |
US6664849B1 (en) * | 1999-07-12 | 2003-12-16 | Mitsubishi Denki Kabushiki Kaisha | Digital FM demodulator performing amplitude compensation |
US6664841B1 (en) * | 2001-03-23 | 2003-12-16 | Conexant Systems, Inc. | Method and apparatus for conditioning an analog signal |
US6707861B1 (en) * | 1999-10-26 | 2004-03-16 | Thomson Licensing S.A. | Demodulator for an HDTV receiver |
US6747581B2 (en) * | 2002-02-01 | 2004-06-08 | Octiv, Inc. | Techniques for variable sample rate conversion |
US6760076B2 (en) * | 2000-12-08 | 2004-07-06 | Koninklijke Philips Electronics N.V. | System and method of synchronization recovery in the presence of pilot carrier phase rotation for an ATSC-HDTV receiver |
US6771707B1 (en) * | 2000-05-11 | 2004-08-03 | Limberg Allen Leroy | Digital television receiver converting vestigial-sideband signals to double-sideband AM signals before demodulation |
US6810084B1 (en) * | 2000-06-12 | 2004-10-26 | Munhwa Broadcasting Corporation | MPEG data frame and transmit and receive system using same |
US6879647B1 (en) * | 2000-09-29 | 2005-04-12 | Northrop Grumman Corporation | Radio receiver AM-MSK processing techniques |
US6937671B2 (en) * | 2000-03-22 | 2005-08-30 | Spacebridge Semiconductor Corporation | Method and system for carrier recovery |
US20050262177A1 (en) * | 2001-10-30 | 2005-11-24 | Zhongnong Jiang | Efficient real-time computation of FIR filter coefficients |
US6972632B2 (en) * | 2002-11-26 | 2005-12-06 | Oki Electric Industry Co., Ltd. | Apparatus for controlling the frequency of received signals to a predetermined frequency |
US7006806B2 (en) * | 2002-02-26 | 2006-02-28 | Broadcom Corporation | System and method for SAP FM demodulation |
US7098967B2 (en) * | 2001-10-02 | 2006-08-29 | Matsushita Electric Industrial Co., Ltd. | Receiving apparatus |
US7119856B2 (en) * | 2001-12-10 | 2006-10-10 | Silicon Integrated Systems Corp. | TV decoder |
US7167215B2 (en) * | 2001-04-16 | 2007-01-23 | Thomson Licensing | Gain control for a high definition television demodulator |
US20070078542A1 (en) * | 2005-10-03 | 2007-04-05 | Sigmatel, Inc. | Method and system for receiving and decoding audio signals |
US7253753B2 (en) * | 2002-02-26 | 2007-08-07 | Broadcom Corporation | Method and apparatus of performing sample rate conversion of a multi-channel audio signal |
US7272197B2 (en) * | 2002-10-01 | 2007-09-18 | Lg Electronics Inc. | Device for recovering carrier |
US7403579B2 (en) * | 1998-11-03 | 2008-07-22 | Broadcom Corporation | Dual mode QAM/VSB receiver |
-
2002
- 2002-02-26 US US10/083,052 patent/US7079657B2/en not_active Expired - Fee Related
-
2006
- 2006-06-27 US US11/426,836 patent/US7912153B2/en not_active Expired - Fee Related
-
2011
- 2011-03-22 US US13/069,090 patent/US20110211658A1/en not_active Abandoned
Patent Citations (74)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4506228A (en) * | 1981-09-26 | 1985-03-19 | Robert Bosch Gmbh | Digital FM detector |
US4486897A (en) * | 1982-02-09 | 1984-12-04 | Sony Corporation | Television receiver for demodulating a two-language stereo broadcast signal |
US4626892A (en) * | 1984-03-05 | 1986-12-02 | Rca Corporation | Television system with menu like function control selection |
US4704726A (en) * | 1984-03-30 | 1987-11-03 | Rca Corporation | Filter arrangement for an audio companding system |
US4716589A (en) * | 1984-11-26 | 1987-12-29 | Nec Corporation | Multivoice signal switching circuit |
US4628539A (en) * | 1985-02-25 | 1986-12-09 | Rca Corporation | Muting circuit |
US4803700A (en) * | 1985-06-12 | 1989-02-07 | U.S. Philips Corp. | Method of, and demodulator for, digitally demodulating an SSB signal |
US4747140A (en) * | 1986-12-24 | 1988-05-24 | Rca Corporation | Low distortion filters for separating frequency or phase modulated signals from composite signals |
US5250748A (en) * | 1986-12-30 | 1993-10-05 | Yamaha Corporation | Tone signal generation device employing a digital filter |
US4862099A (en) * | 1987-08-18 | 1989-08-29 | Mitsubishi Denki Kabushiki Kaisha | Digital FM demodulator with distortion correction |
US5149902A (en) * | 1989-12-07 | 1992-09-22 | Kabushiki Kaisha Kawai Gakki Seisakusho | Electronic musical instrument using filters for timbre control |
US5091957A (en) * | 1990-04-18 | 1992-02-25 | Thomson Consumer Electronics, Inc. | Wideband expander for stereo and SAP signals |
US5151926A (en) * | 1991-05-21 | 1992-09-29 | General Electric Company | Sample timing and carrier frequency estimation circuit for sine-cosine detectors |
US5373562A (en) * | 1992-08-28 | 1994-12-13 | Thomson Consumer Electronics, Inc. | Signal processor for sterophonic signals |
US5404405A (en) * | 1993-08-05 | 1995-04-04 | Hughes Aircraft Company | FM stereo decoder and method using digital signal processing |
US5559513A (en) * | 1993-08-06 | 1996-09-24 | Deutsche Thomson-Brandt Gmbh | Digital sampling rate converter |
US5440269A (en) * | 1993-09-08 | 1995-08-08 | Samsung Electronics Co., Ltd. | Digital FM demodulator having an address circuit for a lookup table |
US6512555B1 (en) * | 1994-05-04 | 2003-01-28 | Samsung Electronics Co., Ltd. | Radio receiver for vestigal-sideband amplitude-modulation digital television signals |
US5614862A (en) * | 1995-10-27 | 1997-03-25 | Icom Incorporated | Digital demodulator for a frequency modulated signal and an amplitude modulated signal |
US6118879A (en) * | 1996-06-07 | 2000-09-12 | That Corporation | BTSC encoder |
US6037993A (en) * | 1997-03-17 | 2000-03-14 | Antec Corporation | Digital BTSC compander system |
US5903482A (en) * | 1997-06-20 | 1999-05-11 | Pioneer Electronic Corp. | Sampling frequency converting system and a method thereof |
US5907295A (en) * | 1997-08-04 | 1999-05-25 | Neomagic Corp. | Audio sample-rate conversion using a linear-interpolation stage with a multi-tap low-pass filter requiring reduced coefficient storage |
US6122380A (en) * | 1997-12-01 | 2000-09-19 | Sony Corporation | Apparatus and method of providing stereo television audio signals |
US20030018472A1 (en) * | 1998-01-08 | 2003-01-23 | Yehuda Hershkovits | Vocoder-based voice recognizer |
US6208671B1 (en) * | 1998-01-20 | 2001-03-27 | Cirrus Logic, Inc. | Asynchronous sample rate converter |
US6295362B1 (en) * | 1998-01-20 | 2001-09-25 | General Instrument Corporation | Direct digital synthesis of FM signals |
US6608902B1 (en) * | 1998-02-07 | 2003-08-19 | Sigmatel, Inc. | Stereo signal separation circuit and application thereof |
US6259482B1 (en) * | 1998-03-11 | 2001-07-10 | Matthew F. Easley | Digital BTSC compander system |
US6611571B1 (en) * | 1998-06-16 | 2003-08-26 | Icom Incorporated | Apparatus and method for demodulating an angle-modulated signal |
US6356598B1 (en) * | 1998-08-26 | 2002-03-12 | Thomson Licensing S.A. | Demodulator for an HDTV receiver |
US6476878B1 (en) * | 1998-10-21 | 2002-11-05 | Scientific-Atlanta, Inc. | Method and apparatus for audio signal processing |
US7403579B2 (en) * | 1998-11-03 | 2008-07-22 | Broadcom Corporation | Dual mode QAM/VSB receiver |
US6542203B1 (en) * | 1998-11-12 | 2003-04-01 | Sony United Kingdom Limited | Digital receiver for receiving and demodulating a plurality of digital signals and method thereof |
US6192086B1 (en) * | 1999-01-14 | 2001-02-20 | Antec Corporation | Digital sub-systems and building blocks for a mostly digital low-cost BTSC compatible encoder |
US6535608B1 (en) * | 1999-05-24 | 2003-03-18 | Sanyo Electric Co., Ltd. | Stereo broadcasting receiving device |
US6584145B1 (en) * | 1999-06-02 | 2003-06-24 | Level One Communications, Inc. | Sample rate converter |
US6492913B2 (en) * | 1999-07-09 | 2002-12-10 | Micronas Gmbh | Method and circuit for decoding an analog audio signal using the BTSC standard |
US6281813B1 (en) * | 1999-07-09 | 2001-08-28 | Micronas Gmbh | Circuit for decoding an analog audio signal |
US6664849B1 (en) * | 1999-07-12 | 2003-12-16 | Mitsubishi Denki Kabushiki Kaisha | Digital FM demodulator performing amplitude compensation |
US6442758B1 (en) * | 1999-09-24 | 2002-08-27 | Convedia Corporation | Multimedia conferencing system having a central processing hub for processing video and audio data for remote users |
US6707861B1 (en) * | 1999-10-26 | 2004-03-16 | Thomson Licensing S.A. | Demodulator for an HDTV receiver |
US20030091194A1 (en) * | 1999-12-08 | 2003-05-15 | Bodo Teichmann | Method and device for processing a stereo audio signal |
US6937671B2 (en) * | 2000-03-22 | 2005-08-30 | Spacebridge Semiconductor Corporation | Method and system for carrier recovery |
US6771707B1 (en) * | 2000-05-11 | 2004-08-03 | Limberg Allen Leroy | Digital television receiver converting vestigial-sideband signals to double-sideband AM signals before demodulation |
US6810084B1 (en) * | 2000-06-12 | 2004-10-26 | Munhwa Broadcasting Corporation | MPEG data frame and transmit and receive system using same |
US6879647B1 (en) * | 2000-09-29 | 2005-04-12 | Northrop Grumman Corporation | Radio receiver AM-MSK processing techniques |
US6552753B1 (en) * | 2000-10-19 | 2003-04-22 | Ilya Zhurbinskiy | Method and apparatus for maintaining uniform sound volume for televisions and other systems |
US6760076B2 (en) * | 2000-12-08 | 2004-07-06 | Koninklijke Philips Electronics N.V. | System and method of synchronization recovery in the presence of pilot carrier phase rotation for an ATSC-HDTV receiver |
US20020140853A1 (en) * | 2001-02-20 | 2002-10-03 | Seungjoon Yang | Sampling rate conversion apparatus and method thereof |
US6664841B1 (en) * | 2001-03-23 | 2003-12-16 | Conexant Systems, Inc. | Method and apparatus for conditioning an analog signal |
US7167215B2 (en) * | 2001-04-16 | 2007-01-23 | Thomson Licensing | Gain control for a high definition television demodulator |
US7098967B2 (en) * | 2001-10-02 | 2006-08-29 | Matsushita Electric Industrial Co., Ltd. | Receiving apparatus |
US20050262177A1 (en) * | 2001-10-30 | 2005-11-24 | Zhongnong Jiang | Efficient real-time computation of FIR filter coefficients |
US20030087618A1 (en) * | 2001-11-08 | 2003-05-08 | Junsong Li | Digital FM stereo decoder and method of operation |
US7119856B2 (en) * | 2001-12-10 | 2006-10-10 | Silicon Integrated Systems Corp. | TV decoder |
US6747581B2 (en) * | 2002-02-01 | 2004-06-08 | Octiv, Inc. | Techniques for variable sample rate conversion |
US20030160905A1 (en) * | 2002-02-26 | 2003-08-28 | Wu David Chaohua | Scaling adjustment to enhance stereo separation |
US20030162517A1 (en) * | 2002-02-26 | 2003-08-28 | Wu David Chaohua | Scaling adjustment using pilot signal |
US7912153B2 (en) * | 2002-02-26 | 2011-03-22 | Broadcom Corp. | System and method of performing digital multi-channel audio signal decoding |
US7006806B2 (en) * | 2002-02-26 | 2006-02-28 | Broadcom Corporation | System and method for SAP FM demodulation |
US7079657B2 (en) * | 2002-02-26 | 2006-07-18 | Broadcom Corporation | System and method of performing digital multi-channel audio signal decoding |
US6859238B2 (en) * | 2002-02-26 | 2005-02-22 | Broadcom Corporation | Scaling adjustment to enhance stereo separation |
US6832078B2 (en) * | 2002-02-26 | 2004-12-14 | Broadcom Corporation | Scaling adjustment using pilot signal |
US20060232868A1 (en) * | 2002-02-26 | 2006-10-19 | Wu David C | System and method of performing digital multi-channel audio signal decoding |
US20030161477A1 (en) * | 2002-02-26 | 2003-08-28 | Wu David Chaohua | System and method of performing digital multi-channel audio signal decoding |
US7650125B2 (en) * | 2002-02-26 | 2010-01-19 | Broadcom Corporation | System and method for SAP FM demodulation |
US7253753B2 (en) * | 2002-02-26 | 2007-08-07 | Broadcom Corporation | Method and apparatus of performing sample rate conversion of a multi-channel audio signal |
US7515889B2 (en) * | 2002-02-26 | 2009-04-07 | Broadcom Corporation | Scaling adjustment using pilot signal |
US20070273563A1 (en) * | 2002-02-26 | 2007-11-29 | Wu David C | Method and apparatus of performing sample rate conversion of a multi-channel audio signal |
US20050094820A1 (en) * | 2002-02-26 | 2005-05-05 | Wu David C. | Scaling adjustment to enhance stereo separation |
US7272197B2 (en) * | 2002-10-01 | 2007-09-18 | Lg Electronics Inc. | Device for recovering carrier |
US6972632B2 (en) * | 2002-11-26 | 2005-12-06 | Oki Electric Industry Co., Ltd. | Apparatus for controlling the frequency of received signals to a predetermined frequency |
US20070078542A1 (en) * | 2005-10-03 | 2007-04-05 | Sigmatel, Inc. | Method and system for receiving and decoding audio signals |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP2608409A1 (en) | 2011-12-20 | 2013-06-26 | Televic Conference NV | Multichannel sample rate converter |
WO2013092140A1 (en) | 2011-12-20 | 2013-06-27 | Televic Conference Nv | Multichannel sample rate converter |
CN107888206A (en) * | 2017-11-09 | 2018-04-06 | 中国电子科技集团公司第二十九研究所 | A kind of AM voice signals demodulating data Audio recovery method and recording method |
Also Published As
Publication number | Publication date |
---|---|
US20060232868A1 (en) | 2006-10-19 |
US20030161477A1 (en) | 2003-08-28 |
US7912153B2 (en) | 2011-03-22 |
US7079657B2 (en) | 2006-07-18 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
US7912153B2 (en) | System and method of performing digital multi-channel audio signal decoding | |
US8089377B2 (en) | Method and apparatus of performing sample rate conversion of a multi-channel audio signal | |
TWI596947B (en) | Television receiver for digital and analog television signals | |
JP3276392B2 (en) | Time discrete stereo decoder | |
JP5032976B2 (en) | Configurable filter for processing TV audio signals | |
US20060079197A1 (en) | System and method for SAP FM demodulation | |
US7929054B2 (en) | Up-sampling television audio signals for encoding | |
US6859238B2 (en) | Scaling adjustment to enhance stereo separation | |
US8050412B2 (en) | Scaling adjustment to enhance stereo separation | |
US7468763B2 (en) | Method and apparatus for digital MTS receiver | |
US20040101143A1 (en) | Method and system for digitally decoding an MTS signal | |
US5239585A (en) | Devices, systems, and methods for composite signal decoding | |
JP2006325217A (en) | Circuit and method for decoding btsc multi-channel tv sound signal | |
EP1349386B1 (en) | Method and apparatus of performing sample rate conversion of a multi-channel audio signal | |
JP4327087B2 (en) | Stereo signal processor | |
JPH0822036B2 (en) | Audio signal processing method and circuit thereof |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
STCB | Information on status: application discontinuation |
Free format text: ABANDONED -- FAILURE TO RESPOND TO AN OFFICE ACTION |
|
AS | Assignment |
Owner name: BANK OF AMERICA, N.A., AS COLLATERAL AGENT, NORTH CAROLINA Free format text: PATENT SECURITY AGREEMENT;ASSIGNOR:BROADCOM CORPORATION;REEL/FRAME:037806/0001 Effective date: 20160201 Owner name: BANK OF AMERICA, N.A., AS COLLATERAL AGENT, NORTH Free format text: PATENT SECURITY AGREEMENT;ASSIGNOR:BROADCOM CORPORATION;REEL/FRAME:037806/0001 Effective date: 20160201 |
|
AS | Assignment |
Owner name: AVAGO TECHNOLOGIES GENERAL IP (SINGAPORE) PTE. LTD., SINGAPORE Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:BROADCOM CORPORATION;REEL/FRAME:041706/0001 Effective date: 20170120 Owner name: AVAGO TECHNOLOGIES GENERAL IP (SINGAPORE) PTE. LTD Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:BROADCOM CORPORATION;REEL/FRAME:041706/0001 Effective date: 20170120 |
|
AS | Assignment |
Owner name: BROADCOM CORPORATION, CALIFORNIA Free format text: TERMINATION AND RELEASE OF SECURITY INTEREST IN PATENTS;ASSIGNOR:BANK OF AMERICA, N.A., AS COLLATERAL AGENT;REEL/FRAME:041712/0001 Effective date: 20170119 |