CA2207073C - Dual frequency global positioning system - Google Patents
Dual frequency global positioning system Download PDFInfo
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- CA2207073C CA2207073C CA002207073A CA2207073A CA2207073C CA 2207073 C CA2207073 C CA 2207073C CA 002207073 A CA002207073 A CA 002207073A CA 2207073 A CA2207073 A CA 2207073A CA 2207073 C CA2207073 C CA 2207073C
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S19/00—Satellite radio beacon positioning systems; Determining position, velocity or attitude using signals transmitted by such systems
- G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
- G01S19/13—Receivers
- G01S19/32—Multimode operation in a single same satellite system, e.g. GPS L1/L2
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S19/00—Satellite radio beacon positioning systems; Determining position, velocity or attitude using signals transmitted by such systems
- G01S19/01—Satellite radio beacon positioning systems transmitting time-stamped messages, e.g. GPS [Global Positioning System], GLONASS [Global Orbiting Navigation Satellite System] or GALILEO
- G01S19/13—Receivers
- G01S19/24—Acquisition or tracking or demodulation of signals transmitted by the system
- G01S19/29—Acquisition or tracking or demodulation of signals transmitted by the system carrier including Doppler, related
Abstract
A global position system receiver recovers the L1 and L2 carriers, the C/A- code measurements and the L1 and L2 P-code measurements by (a) producing an estimate of the L1 carrier phase angle and synchronizing a locally generated C/A-code with the L1 signal using an L1 delay lock loop and controlling, bas ed on the locally generated C/A code, an L1 P-code generator that produces a synchronized version of the P-code; (b) initializing an L2 P-code generator based on the phase of the P-code generated by the L1 P-code generator; (c) determining, for the L2 signal, an estimate of signal power that is adjusted to compensate for noise; (d) determining an L2 carrier phase angle; (e) tracking the L2 P-code by adjusting an L2 P-code generator until the estimat e of signal power is maximized. The GPS receiver also resolves a 1/2 cycle ambiguity in tracking the L2 P-code by comparing demodulated L1 P-code bits and L2 P-code bits. If the bits do not match in the majority of instances, t he receiver determines that it is tracking the L2 P-code with 1/2 cycle error a nd adjusts its estimate of the P-code phase accordingly. The receiver thus trac ks the L2 P-code and carrier independently of the L1 signal, with the exception of the resolution of the 1/2 cycle ambiguity. Accordingly, the receiver can determine the reliability of the L2 signal by determining a carrier-to-noise ratio.
Description
DUAL FREQUENCY GLOBAL POSITIONING SYSTEM
.s FIELD OF THE INVENTION
a This invention relates generally to global positioning systems (GPS) and, more particularly, to receivers that use GPS ranging signals received over an L1 frequency band and an L2 frequency band to determine their positions.
BACKGROUND OF THE INVENTION
A global positioning system (GPS) includes a number of satellites that each transmit ranging signals over L1 and L2 frequency bands. The ranging signals, referred to herein, respectively, as L1 signals and L2 signals, are modulated by pseudo-random bi-phase codes that are unique to the respective satellites. A GPS receiver receives signals from a number of the satellites and, using the associated codes, determines (i) the differences in times of arrival of the transmitted codes, and (ii) the relative phases of the associated carriers. The receiver then uses this information, in a known manner, to determine its position.
The L1 signals produced by a satellite are modulated by a "C/A" code and a higher rate "P" code. The P-code is encrypted with an encryption code that is known only to government-classified users, such as the military. The signals are further modulated by data that conveys to the receiver certain system-related information, such as the satellite s ephemeris (i.e. position), current time of day (typically a standardized time, such as Greenwich Mean Time), and system status information. _ For applications such as navigation that do not require determining "exact" positions, that is, positions to within more than approximately a meter for differential GPS
SUBSTITUTE SHEET (RULE 26) WO 97/14052 PCT/CA9b/00614 calculations, the GPS receiver determines its position based on the code and carrier phase measurements of the L1 signals from at least four satellites. To do this, the receiver aligns locally-generated versions of the applicable C/A-codes and carriers with the received signals. Then, based on the differences in the clocks in the C/A code generators in the receiver and those in the satellites and on the phase measurements of the carrier signal generators, the receiver calculates its position.
Ionospheric refraction, which alters the path of the signals, introduces errors into the calculations that prevent the receiver from determining its position with greater accuracy. If more precise position information is required, for applications such as surveying, for example, the GPS
receiver uses the signals transmitted over both the L1 and the L2 bands.
The ionosphere affects the L1 and L2 signals differently because of the differences in the frequencies of the signals.
Since the relative phases of the L1 and L2 signals are known at transmission, the phase difference between the L1 and L2 signals, when down-converted to the same IF frequency at the receiver, is attributable to ionospheric refraction.
Accordingly, if this phase difference can be accurately determined at the receiver, the receiver can, using a known formula, determine the changes in the signal paths caused by the ionosphere. It can then correct for these changes, and determine its position to within a small number of centimeters or even millimeters. The accuracy with which the receiver can determine its position is based at least in part on the accuracy of the phase information.
A problem that occurs when determining the phases of the L1 or L2 signals is what is referred to as "carrier-cycle ambiguity." Once the receiver has locked onto a carrier, the receiver can not readily determine which cycle it is receiving at any instant in time, since the cycles are ..
SUBSTITUTE SHEET (RULE 26) identical. The full-cycle ambiguity affects the accuracy with which the receiver can determine its position using the L1 signals alone or the L1 and the L2 signals. To resolve the ambiguity based on the L1 signals alone, the receiver must determine, by means of the code timing, its position to within one carrier cycle, which is 19 centimeters. This requires lengthy, time-consuming calculations and an estimate of ionospheric refraction that is based on atmospheric conditions. If both the L1 and L2 signals are used, however, the receiver can resolve the carrier-cycle ambiguity once it determines its position to within one cycle of the L1 minus L2, or beat, frequency, which is 86 centimeters. This reduces the amount of calculation, and thus, the time it takes for the receiver to resolve the ambiguity.
One problem with using the L2 signals is that the code contained therein is encrypted. Accordingly, the receiver cannot recover the L2 carriers using the same decoding operations that are used to recover the L1 carriers, namely, the aligning of the locally-generated C/A codes with the (unencrypted) CJA codes in the received signals. Instead, the receiver must remove the unknown encryption code from the L2 P-codes before it can recover the L2 carriers.
In a prior known system, the received L2 signals are squared, to remove the bi-phase encryption code. This produces an output signal that is twice the frequency of the carrier. The receiver then recovers the carrier from this signal. The problem with squaring the signal is that the noise components of the signal are also squared, which adversely affects the recovery of the carrier. Further, it prevents the tracking of the bi-phase P-code, since this code is also removed by the squaring. The result is a less precise determination of the phase difference between the L1 and L2 signals, and thus, a less precise position determination.
SUBSTITUTE SHEET (RULE 26) Another system has attempted to reduce the affects of the noise by first roughly correlating the L2 signal with a locally-generated version of the P-code, and then squaring ' the result. While this reduces the adverse affects of the noise somewhat, it does not sufficiently alleviate them.
SUMMARY OF THE INVENTION
The invention is a GPS receiver that recovers the L1 and L2 carriers and the respective C/A and P-code measurements by (i) estimating an L1 carrier phase angle tracking error and adjusting an oscillator that produces an estimate of the L1 carrier phase angle; (ii) synchronizing a locally-generated C/A-code with the L1 signal using an L1 delay lock loop (:DLL) and controlling, based on the locally generated C/A code, an L1 P-code generator that produces a synchronized version of the P-code; (iii) initializing an L2 P-code generator based on the phase of the P-code generated by the L1 P-code generator; (iv) determining, for the L2 signal, an estimate of signal power that is adjusted to compensate for noise; (v) determining an L2 carrier phase angle tracking error based on the received signal and the estimated signal power, and adjusting an oscillator that produces an estimate of the L2 carrier phase angle; and (vi) tracking the L2 P-code with an L2 DLL that adjusts the L2 P-code generator until the estimate of signal power is maximized.
More specifically, to decode the L1 signals the receiver splits the signals into baseband inphase (I) and quadrature (Q) components. These components are correlated with, that is, multiplied by, a locally-generated C/A-code. The resulting correlated I and Q signals are then used to estimate the L1 carrier phase angle tracking error as arctan(Q/I). Based on this estimated error, the receiver -adjusts a numerically controlled oscillator (NCO) that produces the estimated Ll carrier phase angle that is used to split the incoming L1 signals into the I and Q components.
The receiver, using a conventional DLL, tracks the C/A-code SUBSTITUTE SHEET (RULE 26) in the received signal by adjusting its C/A-code generator to maximize the values of the resulting correlated I and Q
~ signals.
The L1 P-code generator is phase-locked to the L1 C/A-code generator, based on a known phase relationship between the two codes at the transmitter. Since the relative phases of the Ll and L2 P-codes are also fixed at the transmitter, the L1 P-code is used to initialize the L2 P-code generator.
The L2 P-code generator then produces a P-code that is, except for the affects of ionospheric refraction, in synchronism with the L2 signal. As discussed below, the receiver aligns the locally-generated P-code with the L2 signal based on an estimate of the L2 carrier phase and a determination of signal power.
To decode the L2 signals the receiver splits these signals into inphase (I) and quadrature (Q) components. Each of these components is simultaneously sent along two paths.
In the first path the components are multiplied by the locally-generated version of the P-code. In the second path the components are multiplied by a delayed, or uncorrelated, version of the P-code. This spreads any interference. The first path produces correlated resulting signals, IS=O and Qs=c. and the second path produces uncorrelated resulting signals, Irrozss and QNOISE' The receiver estimates its error in tracking the phase of the L2 carrier based on a phase discriminator output, which includes the product Qs=~*signIs=~, where "signIs=~" is the sign of the component ISIS and "*" represents multiplication. When the codes are aligned and the carrier is phase-locked to the received signal, the ISIS signal is an estimate of the unknown encryption code. Accordingly, the -multiplication removes the estimate of the unknown encryption code from the error calculation.
The product is, however, dependent both on the signal power and on carrier phase angle. Accordingly, the product SUBSTITUTE SHEET (RULE 26) WO 97/14052 PCT/CA9b/00614 must be normalized to remove the signal power dependence, so that the phase angle error can be determined. To do this a normalizing factor, ST, is included in the calculation of the phase error estimate. The normalizing factor is based on an estimate of total signal power, STOT~x,, and is independent of the carrier phase angle.
The receiver estimates STOTaz as ST=SI+ SQ, where SI and SQ are the signal power values associated, respectively, with the I and Q components. These values are determined by th.e equations:
SI = ABS ( ISIG ) - ABS ( INOISE ) SQ = ABS ( QgIG J - ABS ( QNOISE ) ~
where "ABS" represents the absolute value. As discussed i.n more detail below, the noise components eliminate a bias that tends to make ABS(IsIG) and ABS (QsIG) less dependent on total signal power, and thus, inappropriate as normalizing factors.
As also discussed in more detail below, the receiver produ-.ces an estimate of the L2 carrier phase angle tracking error by the formula:
R*signl f 2 l ERI~L2- If2*c~rctan *
Ifl ST
where K1 and KZ are constants that are included, respectively, to ensure that, when no signal is present, all phase angles are equally likely, and to normalize the slope of the arctangent function such that it has a slope of ones at zero phase angle. This error estimate, which approximates the true phase error, is used to adjust the oscillator that produces the estimated L2 carrier phase angle. The receiver tracks the L2 P-code by adjusting the L2 P-code generator to maximize ST.
When the system has locked onto the L2 carrier, SI is substituted for ST in formula 2, since SI is a "quieter"
estimate of the signal power that includes only one-half of the noise that is not eliminated by subtracting the noise components INOxsE and QNOxsE from IsIG and QsIG~
SUBSTITUTE SHEET (RULE 26) Once the carrier phase angle tracking errors are minimized, the receiver resolves the 1/2-cycle ambiguities that are associated with using the arctangents to determine the phase errors. For the L1 signals, the receiver determines if particular bits in the received data have predetermined values. If the bits are inverted, the receiver determines it is tracking with a 1/2-cycle error.
It then adjusts by 1/2 cycle the oscillator that produces the estimated L1 carrier. To resolve the ambiguity for the L2 signals, the receiver compares the demodulated bits of the encrypted L2 P-code with the corresponding demodulated bits of the encrypted L1 P-code. Since the two codes are encrypted with the same encryption code, the ambiguity can be resolved by this comparison. Accordingly, if the majority of bits of the L2 code are inverted from those of the L1 code, the receiver determines that it is tracking the L2 carrier with a 1/2 cycle error. It then appropriately adjusts the oscillator that produces the estimated L2 carrier.
The receiver determines the relative phases of the L1 and L2 carriers from the associated oscillators, and the C/A- and P-code time of arrival measurements from the associated local code generators. It then uses the phase information and the code measurements, in a conventional manner, to (i) resolve the full carrier cycle ambiguities, (ii) correct for ionospheric refraction and (iii) determine its position.
The invention may be summarized according to one broad aspect as a global position sensing receiver for receiving over L1 and L2 bands, respectively, L1 signals 7a that are modulated by a C/A-code and an encrypted P-code and L2 signals that are modulated by the encrypted P-code, the receiver including: A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal; B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code; C. an L2 carrier angle estimation means for producing an estimate of the phase angle of an L2 carrier; D. an L2 P-code generator for producing a locally-generated version of the P-code; E. a controller for controlling the operations of the L2 P-code generator, the controller receiving signals associated with a correlation between the locally-generated P-code and the received L2 signals, and adjusting the L2 P-code generator to align the locally-generated P-code with the L2 signals; and F. a detector for resolving a 1/2-cycle ambiguity in tracking the L2 P-code, the detector including: i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
According to another broad aspect the invention provides a global position sensing receiver for receiving over L1 and L2 bands, respectively, Ll signals that are modulated by a C/A-code and an encrypted P-code and L2 signals that are modulated by the encrypted P-code, the receiver including: A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal; B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version 7b of the C/A-code; C. an L2 P-code generator for producing a locally-generated version of the P-code; D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals; E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means; and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate as:
ERR~2 = Kz * arctan Q * Sagnl K, ST
where and K1 and K2 are constants, I and Q are inphase and quadrature correlation signals, "sign I" represents the sign of the I signal, and ST is an estimate of total signal power, the controller using the error estimate to adjust the L2 carrier angle estimation means.
According to a further broad aspect the invention provides a global position sensing receiver for receiving over L1 and L2 bands, respectively, L1 signals that are modulated both by a C/A-code and a P-code that is, at times, encrypted, and L2 signals that are modulated by the P-code that is, at times, encrypted, the receiver including: A.
means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 Ii 7c signal; B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code; C. an L2 P-code generator for producing a locally-generated version of the P-code; D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals; E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means;
and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate based on an estimate of total signal power, ST, which is determined as a sum of a. signal power in an inphase path minus inphase noise components, and b. signal power in a quadrature path minus quadrature noise components, the controller using the error estimate to adjust the L2 carrier angle estimation means.
BRIEF DESCRIPTION OF THE DRAWINGS
The above and further advantages of the invention may be better understood by referring to the following description in conjunction with the accompanying drawings, in which:
Fig. 1 is a functional block diagram of a GPS
receiver constructed in accordance with the invention;
7d Fig. 2 is a functional block diagram of a phase rotator included in the receiver of Fig. 1;
Fig. 3 is a functional block diagram of a system for resolving a 1/2-cycle ambiguity in the tracking of the -g_ code by the receiver of Fig. 1.
DETAILED DESCRIPTION OF AN_ILLUSTRATIVE EMBODIMENT
Fig. 1 depicts a GPS receiver 1 that receives signals from GPS satellites (not shown) over an antenna 2. The received signals are amplified by an amplifier 4 and split by a splitter 6 into L1 signals and L2 signals. The splitter sends the L1 signals to an L1 down converter 10 and the L2 signals to an L2 down converter 40.
The L1 down converter 10 converts the received L1 signals from the L1 frequency to a frequency that is compatible with an analog-to-digital converter 12. The analog-to-digital converter 12 samples the down converted signal at a rate that satisfies the Nyquist theorem, and produces an associated digital signal, which it sends along a digital bus 13 to a phase rotator 14. The phase rotator 14 receives from a numerically controlled oscillator (NCO) 16 an estimate of the L1 carrier phase angle, ~zl. Based on the estimate, the phase rotator produces baseband inphase (I) and quadrature (Q) signal components.
More specifically, as depicted in Fig. 2, the phase rotator 14 produces from the phase angle estimate ~zl two values, namely, cos(~zl) and sin(~zl) in calculators 103 and 104. Multipliers 105 and 106 multiply these values by the digital signal samples, effectively rotating the samples b:y the phase angle and also 90° relative to one another, to produce the I and Q samples.
Referring again to Fig. 1, the I and Q signal. components are applied to a correlator 20, which separately multiplies the signals by a locally-generated C/A-code produced by a C/A-code generator 18. The resulting I~oRR and Q~o~ signals are separately low pass filtered by filters 22 and 23, to produce IzpF and QzpF signals. The resulting signals are used by a microprocessor 24 in a conventional DLL, part of which operates in software, to produce an adjustment signal for the C/A code generator 18. The signals are also used by the SUBSTITUTE SHEET (RULE 26) _g-microprocessor 24, to determine an estimate of a carrier phase angle tracking error, ERRzl, by computing:
~ ERRL1 = arctan ~ QI,PF/ II~PF ) This error estimate is then used to adjust the NCO 16, to reduce the phase angle tracking error. As is well known to those skilled in the art, the phase angle error estimate may also be used in a conventional manner in the L1 DLL, to provide carrier-aided tracking.
To produce the L1 signal at the satellite, the carrier is modulated by a C/A-code and a P-code that are 90° out of phase. Accordingly, the baseband I components include components of the C/A-code and essentially no P-code components. Conversely, the baseband Q components include components of the P-code and essentially no C/A-code components. Thus, after the C/A-code is removed by the correlator 20, the resulting I~oRR signals are modulated only by the transmitted, system-related data, and the microprocessor 24 extracts the data based on the sign of the ILpF s ignals .
The calculation of phase tracking angle error, ERRL1, using the arctangent results in a 1/2-cycle ambiguity in tracking the C/A code. This means that the NCO 16 may be tracking the carrier with a 1/2-cycle error. The microprocessor 24 resolves the ambiguity by examining bits of the transmitted data to determine if particular bits have their expected values. If these bits are inverted, the system is tracking with a 1/2-cycle error. This error is corrected by appropriately adjusting the NCO 16.
The microprocessor 24 continues to track the C/A-code by adjusting the C/A-code generator 18 to maximize the values of the IzPF and QzpF signals. _ Once the receiver 1 is tracking the C/A code, the microprocessor 24 initializes an L1 P-code generator 26 based on timing information included in the data. Using the known phase relationship between the C/A- and P- codes in the L1 SUBSTITUTE SHEET (RULE 26) band, the microprocessor 24 phase locks the L1 P-code generator 26 to the L1 C/A-code generator 18, and no further adjustments of the L1 P-code generator 26 are necessary.
The microprocessor 24 then initializes the L2 P-code generator 48 based on the phase of the locally-generated L1 P-code. Since the relative phases of the two codes are fixed at transmission, the L2 P-code generator 48 produces a P-code that is, except for the affects of ionospheric refraction, in synchronism with the L2 signal. To align the locally generated P-code with the L2 signal, the microprocessor determines the L2 carrier phase angle and total signal power and, as discussed below, adjusts the L2 P-code generator to maximize signal power.
Referring still to Fig. 1, the L2 down converter 40 converts the received L2 signal from the L2 frequency to a frequency that is compatible with an analog-to-digital converter 42. The analog-to-digital converter 42 samples the down converted signal at a rate that satisfies the Nyquist theorem, and produces an associated digital signal that it sends along a digital bus 43 to a phase rotator 44. The phase rotator 44 also receives an estimate of the L2 carrier phase angle from an NCO 46, and produces baseband I and Q
signal components. The rotator 44 operates in the same manner as phase rotator 14, which is discussed above with reference to Fig. 2.
The I and Q signal components are each, respectively, sent along two paths 47a-b and 48a-b, to correlators 50 a.nd 52 (the I components) and correlators 54 and 56 (the Q
components). The I and Q signal components that are sent., respectively, to correlators 52 and 54 are multiplied by the correlated version of the locally-generated P-code produced by the L2 P-code generator 48. This removes the P-code components of the received signals, and produces ISIS and Qs=c signals that are modulated only by the unknown encryption code. The ISIS and QS=~ signals are low pass filtered by SUBSTITUTE SHEET (RULE 26) variable low pass filters 60 and 62, to a bandwidth that is appropriate for the estimated encryption code bit rate. This produces IgIG(I,PF) and QSIG(I~PF) ~ that, as discussed below, are used to estimate the phase angle tracking error, ERRz2.
The I and Q signal components that are sent to correlators 50 and 56 are multiplied by an uncorrelated version of the P-code. This spreads any interfering signals that may be present in the received signal. To produce the uncorrelated version of the P-code, a delay 65 delays by more than 2 code chips the code produced by the P-code generator 48. The length of the delay is selected such that, under normal operating conditions for the receiver, there is no correlation expected between the received signal and the delayed version of the signal. The resulting uncorrelated signals, INOZSS and QNOxss. are filtered by variable low pass filters 58 and 64 to a bandwidth that is appropriate for the estimated encryption code bit rate. The results, IpOISE(LPF~
and QNOiss(LPF~ ~ are then used in conjunction with the Is=~ and Qsic signals, to determine the phase discriminator output, which approximates the L2 carrier phase angle tracking error, ERRz2 .
Specifically, a multiplier 82 multiplies QSIC(zPF~ bY the sign of ISIS, to remove an estimate of the encryption code.
The result is low pass filtered by low pass filter 84, to produce (Qs=c(=,PF~~'sign Is=c)zpF- This product is proportional to both signal power and the estimated phase angle.
Accordingly, before this product can be used to estimate the carrier phase angle tracking error, it must be made independent of signal power. The quantity is thus divided by a normalizing signal that is proportional to signal power.
The normalizing signal, ST is an estimate of the total signal power, STOTai,~ The estimated ST is the sum of the signal power in the inphase path, S~, and the signal power in the quadrature path, SQ, determined over intervals set by the SUBSTITUTE SHEET (RULE 26) WO 97/14052 PCT/CA96~/00614 estimated encryption code bit rate. These quantities are calculated as:
SI = ABS ( IgIG(LPF) ) - ABS ( IpOISE (LPF) ) SQ = ABS(QSIG(LPF)) - ABS(QNOISE(LPF)) where ABS( ) is the absolute value. As discussed below, SI ' may be substituted for ST when the tracking error, ERRLZ, is small.
Summers 76 and 86, respectively, subtract the absolui~e value of the noise components from the absolute value of i:he appropriate correlated signals. This removes biases that would otherwise dominate the signal mean throughout the G1?S
signal range when baseband down-conversion is used. These' biases tend to reduce the dependency of the absolute value's of the correlated signals on signal power, and thus, makes them inappropriate for use as normalizing signals. The biases cannot be removed by filtering, however, because the low pass filtering is limited by the expected 500kHz encryption code chip rate.
The absolute values of the signals are calculated by rectifying the signals in rectifiers 66, 68, 72 and 74. The rectification, which is a "distorted squaring," produces SI
and SQ signals that are proportional both to signal power and, respectively, to cos2(Q~LZ) and sin2(~LZ), where ~ is the estimated phase angle. The estimated total signal power, ST, produced in summer 78 is independent of the carrier tracking phase angle since cosz(~L2) + sin2(øLZ) = 1.
The system low pass filters ST, to produce ST(LPF), which is used to normalize the product Q * signs. The normalized product is then used to determine an estimate for the L2 carrier tracking phase angle error, ERRL2:
Q*signl ER.RL2=If2*arctan *
where K1 and K2 are constants.
SUBSTITUTE SHEET (RULE 26) The constant K1 is required to map the probability density function (PDF) of the arctangent of the quotient to a uniform PDF when no signal is present. This ensures that all phase angles are equally likely before signal acquisition.
Without K1, the variances of (QS=c(LPF>*sign IzPF.)~pFand ST~zpF~ are not equal, and the PDF of the arctangent function peaks at zero degrees. This indicates that certain phase angles are more likely than others, and thus, that the error calculation would tend to drive the estimated carrier to these particular angles.
K1 can be determined at start-up, that is, before the signal is acquired, by dividing an analytically determined standard deviation equation for the numerator (QSIC(zPF~*sign ILPF)LPF bY an analytically determined standard deviation equation for the denominator ST~LpF.~. Alternatively, K1 can be determined by mathematical analysis of the receiver or by Monte Carlo analysis.
The constant K2 is required to make the slope of the phase discriminator output one at zero phase. This constant is the inverse of the derivative of the equation for the analytical mean of the arctangent function, evaluated at zero carrier phase angle tracking offset and with the tracking loop update rate and signal level such that the standard deviation of the carrier phase angle tracking error is small (i.e., less than 10°). Alternatively, KZ may be determined by mathematical analysis of the receiver or by Monte Carlo analysis.
Once lock is acquired, and thus, the phase angle is known, the inphase signal power, S=, is used as the -normalizing signal instead of ST, since SI has a lower variance than ST within a reasonable carrier phase tracking error range. A summer 88, which is under the control of the microprocessor 24, allows SQ to be added into the SUBSTITUTE SHEET (RULE 26~
WO 97/14052 PCT/CAf6/00614 calculations for the normalizing signal before lock is acquired and inhibits its inclusion after lock is acquired.
Using S= as the normalizing signal effectively lowers the threshold for loss of lock, because of the lower variance. Further, the resulting mean of the phase angle estimate is proportional to tan (~z2), which results on a more linear angle estimation than that produced when ST is used as the normalizing signal.
The receiver uses a DLL, in a conventional manner, to track the L2 P-code by adjusting the phase of the L2 P-code generator 48 to maximize ST~zpp~. This tracking method eliminates the data transmitted over the L2 band. As discussed above, using the arctangent to calculate the phase error estimate results in a 1/2-cycle ambiguity. To reso7_ve this ambiguity without the data bits, a detector 31 compares demodulated code bits from the encrypted L1 and L2 P-codes.
If the L2 P-code bits are inverted, the NCO 46 is adjusted.
Referring now to Fig. 3, the detector 32 compares, in circuit 200, the demodulated bits of the encrypted L1 P-code with the same bits of the encrypted L2 P-code. Delays 202 and 204, respectively, delay the bits from the Ll code and the L2 code, to compensate for differences in signal propagation, and thus, align the bits. The delays 202 anc9 204, which are under the control of the microprocessor 24, are together equal to the phase difference between.the L1 and L2 codes produced by the L1 and L2 P-code generators.
The compare circuit 200 compares the signs of the aligned bits and provides for each set of bits a match or no _ match signal. Based on these signals, a majority vote circuit 206 produces a vote signal that represents by its state whether the majority of bits match or do not match.
The microprocessor 24 periodically samples the vote signal SUBSTITUTE SHEET (RULE 26) and, if the vote signal signifies that the majority of bits do not match, the microprocessor adjusts the NCO 46.
The comparison of the L1 and L2 P-code bits can be made at the P-code rate or at the estimated encryption code rate.
However, the signal strength is greater when the comparisons are made at the narrower bandwidth of the encryption code rate.
Referring also to Fig. 1, the delay 65 should be selected such that it delays the code by a number of chips that is beyond the chip range through which the receiver searches for the L2 P-code. Otherwise, if the locally-generated code and the received signal are out of synchronism by a number of chips that is equal or close to that used in delay 65, the receiver may detect correlation power in the IrrozsE and QNOiss signals when the received signal is multiplied by the delayed code. When this occurs, the Is=c and QS=~ signals, which are produced by multiplying the I and Q signals by a version of the code that is not delayed, and thus, not correlated with the received signal, are noise.
This means that the signals representing the demodulated P-code 'bits" are also noise. When these "bits" are compared, in the detector 32, to the demodulated Ll P-code bits, the result is approximately equal numbers of matches and no matches. This, in turn, results in essentially periodic adjustment of the phase of the NCO 46 by one-half cycle.
If the detector 32 detects equal numbers of matches and no matches, the microprocessor 24 may shift the L2 P-code generator by the number of chips that corresponds to the delay 65. This results in correlation power being detected in the Is=G and Qs=G signals, instead of in the INOxsE and QrroxsE signals. Similarly, if the detector determines that the numbers of matches and no matches vary by relatively small amounts, the microprocessor 24 may shift the code SUBSTITUTE SHEET (RULE 26) generator 48 by an amount that is slightly less than the number of chips that correspond to the delay 65.
The 1/2 cycle detector 32 may also be used to resolve 1/2 cycle ambiguities that arise in receivers that track 'the L2 P-code but use alternative methods to determine the L2 carrier phase. For example, the 1/2 cycle detector may be used in systems that track the L2 P-code and remove it from the signal, and then square the resulting signal to recover the L2 carrier.
Once the receiver is tracking the C/A code and the L1 and L2 P=codes and carriers, it determines the L1 code and phase measurement signals, respectively, from the L1 code and carrier generators 16, 18 and 26 and the L2 code and phase measurements from the L2 code and carrier generators 48 and 46. Using these measurements, the receiver resolves the :full cycle ambiguities, corrects for ionospheric refraction and determines its position. Further, since the L2 code and phase measurements are determined independently from the :G1 measurements, with the exception of the resolution of the 1/2 cycle ambiguity, the receiver can determine carrier-to-noise ratios for each band. It can thus determine the reliability of each of the L1 and L2 signals.
The foregoing description has been limited to a specific embodiment of this invention. It will be apparent, however, that variations and modifications may be made to the invention, with the attainment of some or all of its advantages. Therefore, it is the object of the appended claims to cover all such variations and modifications as come within the true spirit and scope of the invention.
SUBSTITUTE SHEET (RULE 26)
.s FIELD OF THE INVENTION
a This invention relates generally to global positioning systems (GPS) and, more particularly, to receivers that use GPS ranging signals received over an L1 frequency band and an L2 frequency band to determine their positions.
BACKGROUND OF THE INVENTION
A global positioning system (GPS) includes a number of satellites that each transmit ranging signals over L1 and L2 frequency bands. The ranging signals, referred to herein, respectively, as L1 signals and L2 signals, are modulated by pseudo-random bi-phase codes that are unique to the respective satellites. A GPS receiver receives signals from a number of the satellites and, using the associated codes, determines (i) the differences in times of arrival of the transmitted codes, and (ii) the relative phases of the associated carriers. The receiver then uses this information, in a known manner, to determine its position.
The L1 signals produced by a satellite are modulated by a "C/A" code and a higher rate "P" code. The P-code is encrypted with an encryption code that is known only to government-classified users, such as the military. The signals are further modulated by data that conveys to the receiver certain system-related information, such as the satellite s ephemeris (i.e. position), current time of day (typically a standardized time, such as Greenwich Mean Time), and system status information. _ For applications such as navigation that do not require determining "exact" positions, that is, positions to within more than approximately a meter for differential GPS
SUBSTITUTE SHEET (RULE 26) WO 97/14052 PCT/CA9b/00614 calculations, the GPS receiver determines its position based on the code and carrier phase measurements of the L1 signals from at least four satellites. To do this, the receiver aligns locally-generated versions of the applicable C/A-codes and carriers with the received signals. Then, based on the differences in the clocks in the C/A code generators in the receiver and those in the satellites and on the phase measurements of the carrier signal generators, the receiver calculates its position.
Ionospheric refraction, which alters the path of the signals, introduces errors into the calculations that prevent the receiver from determining its position with greater accuracy. If more precise position information is required, for applications such as surveying, for example, the GPS
receiver uses the signals transmitted over both the L1 and the L2 bands.
The ionosphere affects the L1 and L2 signals differently because of the differences in the frequencies of the signals.
Since the relative phases of the L1 and L2 signals are known at transmission, the phase difference between the L1 and L2 signals, when down-converted to the same IF frequency at the receiver, is attributable to ionospheric refraction.
Accordingly, if this phase difference can be accurately determined at the receiver, the receiver can, using a known formula, determine the changes in the signal paths caused by the ionosphere. It can then correct for these changes, and determine its position to within a small number of centimeters or even millimeters. The accuracy with which the receiver can determine its position is based at least in part on the accuracy of the phase information.
A problem that occurs when determining the phases of the L1 or L2 signals is what is referred to as "carrier-cycle ambiguity." Once the receiver has locked onto a carrier, the receiver can not readily determine which cycle it is receiving at any instant in time, since the cycles are ..
SUBSTITUTE SHEET (RULE 26) identical. The full-cycle ambiguity affects the accuracy with which the receiver can determine its position using the L1 signals alone or the L1 and the L2 signals. To resolve the ambiguity based on the L1 signals alone, the receiver must determine, by means of the code timing, its position to within one carrier cycle, which is 19 centimeters. This requires lengthy, time-consuming calculations and an estimate of ionospheric refraction that is based on atmospheric conditions. If both the L1 and L2 signals are used, however, the receiver can resolve the carrier-cycle ambiguity once it determines its position to within one cycle of the L1 minus L2, or beat, frequency, which is 86 centimeters. This reduces the amount of calculation, and thus, the time it takes for the receiver to resolve the ambiguity.
One problem with using the L2 signals is that the code contained therein is encrypted. Accordingly, the receiver cannot recover the L2 carriers using the same decoding operations that are used to recover the L1 carriers, namely, the aligning of the locally-generated C/A codes with the (unencrypted) CJA codes in the received signals. Instead, the receiver must remove the unknown encryption code from the L2 P-codes before it can recover the L2 carriers.
In a prior known system, the received L2 signals are squared, to remove the bi-phase encryption code. This produces an output signal that is twice the frequency of the carrier. The receiver then recovers the carrier from this signal. The problem with squaring the signal is that the noise components of the signal are also squared, which adversely affects the recovery of the carrier. Further, it prevents the tracking of the bi-phase P-code, since this code is also removed by the squaring. The result is a less precise determination of the phase difference between the L1 and L2 signals, and thus, a less precise position determination.
SUBSTITUTE SHEET (RULE 26) Another system has attempted to reduce the affects of the noise by first roughly correlating the L2 signal with a locally-generated version of the P-code, and then squaring ' the result. While this reduces the adverse affects of the noise somewhat, it does not sufficiently alleviate them.
SUMMARY OF THE INVENTION
The invention is a GPS receiver that recovers the L1 and L2 carriers and the respective C/A and P-code measurements by (i) estimating an L1 carrier phase angle tracking error and adjusting an oscillator that produces an estimate of the L1 carrier phase angle; (ii) synchronizing a locally-generated C/A-code with the L1 signal using an L1 delay lock loop (:DLL) and controlling, based on the locally generated C/A code, an L1 P-code generator that produces a synchronized version of the P-code; (iii) initializing an L2 P-code generator based on the phase of the P-code generated by the L1 P-code generator; (iv) determining, for the L2 signal, an estimate of signal power that is adjusted to compensate for noise; (v) determining an L2 carrier phase angle tracking error based on the received signal and the estimated signal power, and adjusting an oscillator that produces an estimate of the L2 carrier phase angle; and (vi) tracking the L2 P-code with an L2 DLL that adjusts the L2 P-code generator until the estimate of signal power is maximized.
More specifically, to decode the L1 signals the receiver splits the signals into baseband inphase (I) and quadrature (Q) components. These components are correlated with, that is, multiplied by, a locally-generated C/A-code. The resulting correlated I and Q signals are then used to estimate the L1 carrier phase angle tracking error as arctan(Q/I). Based on this estimated error, the receiver -adjusts a numerically controlled oscillator (NCO) that produces the estimated Ll carrier phase angle that is used to split the incoming L1 signals into the I and Q components.
The receiver, using a conventional DLL, tracks the C/A-code SUBSTITUTE SHEET (RULE 26) in the received signal by adjusting its C/A-code generator to maximize the values of the resulting correlated I and Q
~ signals.
The L1 P-code generator is phase-locked to the L1 C/A-code generator, based on a known phase relationship between the two codes at the transmitter. Since the relative phases of the Ll and L2 P-codes are also fixed at the transmitter, the L1 P-code is used to initialize the L2 P-code generator.
The L2 P-code generator then produces a P-code that is, except for the affects of ionospheric refraction, in synchronism with the L2 signal. As discussed below, the receiver aligns the locally-generated P-code with the L2 signal based on an estimate of the L2 carrier phase and a determination of signal power.
To decode the L2 signals the receiver splits these signals into inphase (I) and quadrature (Q) components. Each of these components is simultaneously sent along two paths.
In the first path the components are multiplied by the locally-generated version of the P-code. In the second path the components are multiplied by a delayed, or uncorrelated, version of the P-code. This spreads any interference. The first path produces correlated resulting signals, IS=O and Qs=c. and the second path produces uncorrelated resulting signals, Irrozss and QNOISE' The receiver estimates its error in tracking the phase of the L2 carrier based on a phase discriminator output, which includes the product Qs=~*signIs=~, where "signIs=~" is the sign of the component ISIS and "*" represents multiplication. When the codes are aligned and the carrier is phase-locked to the received signal, the ISIS signal is an estimate of the unknown encryption code. Accordingly, the -multiplication removes the estimate of the unknown encryption code from the error calculation.
The product is, however, dependent both on the signal power and on carrier phase angle. Accordingly, the product SUBSTITUTE SHEET (RULE 26) WO 97/14052 PCT/CA9b/00614 must be normalized to remove the signal power dependence, so that the phase angle error can be determined. To do this a normalizing factor, ST, is included in the calculation of the phase error estimate. The normalizing factor is based on an estimate of total signal power, STOT~x,, and is independent of the carrier phase angle.
The receiver estimates STOTaz as ST=SI+ SQ, where SI and SQ are the signal power values associated, respectively, with the I and Q components. These values are determined by th.e equations:
SI = ABS ( ISIG ) - ABS ( INOISE ) SQ = ABS ( QgIG J - ABS ( QNOISE ) ~
where "ABS" represents the absolute value. As discussed i.n more detail below, the noise components eliminate a bias that tends to make ABS(IsIG) and ABS (QsIG) less dependent on total signal power, and thus, inappropriate as normalizing factors.
As also discussed in more detail below, the receiver produ-.ces an estimate of the L2 carrier phase angle tracking error by the formula:
R*signl f 2 l ERI~L2- If2*c~rctan *
Ifl ST
where K1 and KZ are constants that are included, respectively, to ensure that, when no signal is present, all phase angles are equally likely, and to normalize the slope of the arctangent function such that it has a slope of ones at zero phase angle. This error estimate, which approximates the true phase error, is used to adjust the oscillator that produces the estimated L2 carrier phase angle. The receiver tracks the L2 P-code by adjusting the L2 P-code generator to maximize ST.
When the system has locked onto the L2 carrier, SI is substituted for ST in formula 2, since SI is a "quieter"
estimate of the signal power that includes only one-half of the noise that is not eliminated by subtracting the noise components INOxsE and QNOxsE from IsIG and QsIG~
SUBSTITUTE SHEET (RULE 26) Once the carrier phase angle tracking errors are minimized, the receiver resolves the 1/2-cycle ambiguities that are associated with using the arctangents to determine the phase errors. For the L1 signals, the receiver determines if particular bits in the received data have predetermined values. If the bits are inverted, the receiver determines it is tracking with a 1/2-cycle error.
It then adjusts by 1/2 cycle the oscillator that produces the estimated L1 carrier. To resolve the ambiguity for the L2 signals, the receiver compares the demodulated bits of the encrypted L2 P-code with the corresponding demodulated bits of the encrypted L1 P-code. Since the two codes are encrypted with the same encryption code, the ambiguity can be resolved by this comparison. Accordingly, if the majority of bits of the L2 code are inverted from those of the L1 code, the receiver determines that it is tracking the L2 carrier with a 1/2 cycle error. It then appropriately adjusts the oscillator that produces the estimated L2 carrier.
The receiver determines the relative phases of the L1 and L2 carriers from the associated oscillators, and the C/A- and P-code time of arrival measurements from the associated local code generators. It then uses the phase information and the code measurements, in a conventional manner, to (i) resolve the full carrier cycle ambiguities, (ii) correct for ionospheric refraction and (iii) determine its position.
The invention may be summarized according to one broad aspect as a global position sensing receiver for receiving over L1 and L2 bands, respectively, L1 signals 7a that are modulated by a C/A-code and an encrypted P-code and L2 signals that are modulated by the encrypted P-code, the receiver including: A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal; B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code; C. an L2 carrier angle estimation means for producing an estimate of the phase angle of an L2 carrier; D. an L2 P-code generator for producing a locally-generated version of the P-code; E. a controller for controlling the operations of the L2 P-code generator, the controller receiving signals associated with a correlation between the locally-generated P-code and the received L2 signals, and adjusting the L2 P-code generator to align the locally-generated P-code with the L2 signals; and F. a detector for resolving a 1/2-cycle ambiguity in tracking the L2 P-code, the detector including: i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
According to another broad aspect the invention provides a global position sensing receiver for receiving over L1 and L2 bands, respectively, Ll signals that are modulated by a C/A-code and an encrypted P-code and L2 signals that are modulated by the encrypted P-code, the receiver including: A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal; B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version 7b of the C/A-code; C. an L2 P-code generator for producing a locally-generated version of the P-code; D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals; E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means; and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate as:
ERR~2 = Kz * arctan Q * Sagnl K, ST
where and K1 and K2 are constants, I and Q are inphase and quadrature correlation signals, "sign I" represents the sign of the I signal, and ST is an estimate of total signal power, the controller using the error estimate to adjust the L2 carrier angle estimation means.
According to a further broad aspect the invention provides a global position sensing receiver for receiving over L1 and L2 bands, respectively, L1 signals that are modulated both by a C/A-code and a P-code that is, at times, encrypted, and L2 signals that are modulated by the P-code that is, at times, encrypted, the receiver including: A.
means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 Ii 7c signal; B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code; C. an L2 P-code generator for producing a locally-generated version of the P-code; D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals; E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means;
and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate based on an estimate of total signal power, ST, which is determined as a sum of a. signal power in an inphase path minus inphase noise components, and b. signal power in a quadrature path minus quadrature noise components, the controller using the error estimate to adjust the L2 carrier angle estimation means.
BRIEF DESCRIPTION OF THE DRAWINGS
The above and further advantages of the invention may be better understood by referring to the following description in conjunction with the accompanying drawings, in which:
Fig. 1 is a functional block diagram of a GPS
receiver constructed in accordance with the invention;
7d Fig. 2 is a functional block diagram of a phase rotator included in the receiver of Fig. 1;
Fig. 3 is a functional block diagram of a system for resolving a 1/2-cycle ambiguity in the tracking of the -g_ code by the receiver of Fig. 1.
DETAILED DESCRIPTION OF AN_ILLUSTRATIVE EMBODIMENT
Fig. 1 depicts a GPS receiver 1 that receives signals from GPS satellites (not shown) over an antenna 2. The received signals are amplified by an amplifier 4 and split by a splitter 6 into L1 signals and L2 signals. The splitter sends the L1 signals to an L1 down converter 10 and the L2 signals to an L2 down converter 40.
The L1 down converter 10 converts the received L1 signals from the L1 frequency to a frequency that is compatible with an analog-to-digital converter 12. The analog-to-digital converter 12 samples the down converted signal at a rate that satisfies the Nyquist theorem, and produces an associated digital signal, which it sends along a digital bus 13 to a phase rotator 14. The phase rotator 14 receives from a numerically controlled oscillator (NCO) 16 an estimate of the L1 carrier phase angle, ~zl. Based on the estimate, the phase rotator produces baseband inphase (I) and quadrature (Q) signal components.
More specifically, as depicted in Fig. 2, the phase rotator 14 produces from the phase angle estimate ~zl two values, namely, cos(~zl) and sin(~zl) in calculators 103 and 104. Multipliers 105 and 106 multiply these values by the digital signal samples, effectively rotating the samples b:y the phase angle and also 90° relative to one another, to produce the I and Q samples.
Referring again to Fig. 1, the I and Q signal. components are applied to a correlator 20, which separately multiplies the signals by a locally-generated C/A-code produced by a C/A-code generator 18. The resulting I~oRR and Q~o~ signals are separately low pass filtered by filters 22 and 23, to produce IzpF and QzpF signals. The resulting signals are used by a microprocessor 24 in a conventional DLL, part of which operates in software, to produce an adjustment signal for the C/A code generator 18. The signals are also used by the SUBSTITUTE SHEET (RULE 26) _g-microprocessor 24, to determine an estimate of a carrier phase angle tracking error, ERRzl, by computing:
~ ERRL1 = arctan ~ QI,PF/ II~PF ) This error estimate is then used to adjust the NCO 16, to reduce the phase angle tracking error. As is well known to those skilled in the art, the phase angle error estimate may also be used in a conventional manner in the L1 DLL, to provide carrier-aided tracking.
To produce the L1 signal at the satellite, the carrier is modulated by a C/A-code and a P-code that are 90° out of phase. Accordingly, the baseband I components include components of the C/A-code and essentially no P-code components. Conversely, the baseband Q components include components of the P-code and essentially no C/A-code components. Thus, after the C/A-code is removed by the correlator 20, the resulting I~oRR signals are modulated only by the transmitted, system-related data, and the microprocessor 24 extracts the data based on the sign of the ILpF s ignals .
The calculation of phase tracking angle error, ERRL1, using the arctangent results in a 1/2-cycle ambiguity in tracking the C/A code. This means that the NCO 16 may be tracking the carrier with a 1/2-cycle error. The microprocessor 24 resolves the ambiguity by examining bits of the transmitted data to determine if particular bits have their expected values. If these bits are inverted, the system is tracking with a 1/2-cycle error. This error is corrected by appropriately adjusting the NCO 16.
The microprocessor 24 continues to track the C/A-code by adjusting the C/A-code generator 18 to maximize the values of the IzPF and QzpF signals. _ Once the receiver 1 is tracking the C/A code, the microprocessor 24 initializes an L1 P-code generator 26 based on timing information included in the data. Using the known phase relationship between the C/A- and P- codes in the L1 SUBSTITUTE SHEET (RULE 26) band, the microprocessor 24 phase locks the L1 P-code generator 26 to the L1 C/A-code generator 18, and no further adjustments of the L1 P-code generator 26 are necessary.
The microprocessor 24 then initializes the L2 P-code generator 48 based on the phase of the locally-generated L1 P-code. Since the relative phases of the two codes are fixed at transmission, the L2 P-code generator 48 produces a P-code that is, except for the affects of ionospheric refraction, in synchronism with the L2 signal. To align the locally generated P-code with the L2 signal, the microprocessor determines the L2 carrier phase angle and total signal power and, as discussed below, adjusts the L2 P-code generator to maximize signal power.
Referring still to Fig. 1, the L2 down converter 40 converts the received L2 signal from the L2 frequency to a frequency that is compatible with an analog-to-digital converter 42. The analog-to-digital converter 42 samples the down converted signal at a rate that satisfies the Nyquist theorem, and produces an associated digital signal that it sends along a digital bus 43 to a phase rotator 44. The phase rotator 44 also receives an estimate of the L2 carrier phase angle from an NCO 46, and produces baseband I and Q
signal components. The rotator 44 operates in the same manner as phase rotator 14, which is discussed above with reference to Fig. 2.
The I and Q signal components are each, respectively, sent along two paths 47a-b and 48a-b, to correlators 50 a.nd 52 (the I components) and correlators 54 and 56 (the Q
components). The I and Q signal components that are sent., respectively, to correlators 52 and 54 are multiplied by the correlated version of the locally-generated P-code produced by the L2 P-code generator 48. This removes the P-code components of the received signals, and produces ISIS and Qs=c signals that are modulated only by the unknown encryption code. The ISIS and QS=~ signals are low pass filtered by SUBSTITUTE SHEET (RULE 26) variable low pass filters 60 and 62, to a bandwidth that is appropriate for the estimated encryption code bit rate. This produces IgIG(I,PF) and QSIG(I~PF) ~ that, as discussed below, are used to estimate the phase angle tracking error, ERRz2.
The I and Q signal components that are sent to correlators 50 and 56 are multiplied by an uncorrelated version of the P-code. This spreads any interfering signals that may be present in the received signal. To produce the uncorrelated version of the P-code, a delay 65 delays by more than 2 code chips the code produced by the P-code generator 48. The length of the delay is selected such that, under normal operating conditions for the receiver, there is no correlation expected between the received signal and the delayed version of the signal. The resulting uncorrelated signals, INOZSS and QNOxss. are filtered by variable low pass filters 58 and 64 to a bandwidth that is appropriate for the estimated encryption code bit rate. The results, IpOISE(LPF~
and QNOiss(LPF~ ~ are then used in conjunction with the Is=~ and Qsic signals, to determine the phase discriminator output, which approximates the L2 carrier phase angle tracking error, ERRz2 .
Specifically, a multiplier 82 multiplies QSIC(zPF~ bY the sign of ISIS, to remove an estimate of the encryption code.
The result is low pass filtered by low pass filter 84, to produce (Qs=c(=,PF~~'sign Is=c)zpF- This product is proportional to both signal power and the estimated phase angle.
Accordingly, before this product can be used to estimate the carrier phase angle tracking error, it must be made independent of signal power. The quantity is thus divided by a normalizing signal that is proportional to signal power.
The normalizing signal, ST is an estimate of the total signal power, STOTai,~ The estimated ST is the sum of the signal power in the inphase path, S~, and the signal power in the quadrature path, SQ, determined over intervals set by the SUBSTITUTE SHEET (RULE 26) WO 97/14052 PCT/CA96~/00614 estimated encryption code bit rate. These quantities are calculated as:
SI = ABS ( IgIG(LPF) ) - ABS ( IpOISE (LPF) ) SQ = ABS(QSIG(LPF)) - ABS(QNOISE(LPF)) where ABS( ) is the absolute value. As discussed below, SI ' may be substituted for ST when the tracking error, ERRLZ, is small.
Summers 76 and 86, respectively, subtract the absolui~e value of the noise components from the absolute value of i:he appropriate correlated signals. This removes biases that would otherwise dominate the signal mean throughout the G1?S
signal range when baseband down-conversion is used. These' biases tend to reduce the dependency of the absolute value's of the correlated signals on signal power, and thus, makes them inappropriate for use as normalizing signals. The biases cannot be removed by filtering, however, because the low pass filtering is limited by the expected 500kHz encryption code chip rate.
The absolute values of the signals are calculated by rectifying the signals in rectifiers 66, 68, 72 and 74. The rectification, which is a "distorted squaring," produces SI
and SQ signals that are proportional both to signal power and, respectively, to cos2(Q~LZ) and sin2(~LZ), where ~ is the estimated phase angle. The estimated total signal power, ST, produced in summer 78 is independent of the carrier tracking phase angle since cosz(~L2) + sin2(øLZ) = 1.
The system low pass filters ST, to produce ST(LPF), which is used to normalize the product Q * signs. The normalized product is then used to determine an estimate for the L2 carrier tracking phase angle error, ERRL2:
Q*signl ER.RL2=If2*arctan *
where K1 and K2 are constants.
SUBSTITUTE SHEET (RULE 26) The constant K1 is required to map the probability density function (PDF) of the arctangent of the quotient to a uniform PDF when no signal is present. This ensures that all phase angles are equally likely before signal acquisition.
Without K1, the variances of (QS=c(LPF>*sign IzPF.)~pFand ST~zpF~ are not equal, and the PDF of the arctangent function peaks at zero degrees. This indicates that certain phase angles are more likely than others, and thus, that the error calculation would tend to drive the estimated carrier to these particular angles.
K1 can be determined at start-up, that is, before the signal is acquired, by dividing an analytically determined standard deviation equation for the numerator (QSIC(zPF~*sign ILPF)LPF bY an analytically determined standard deviation equation for the denominator ST~LpF.~. Alternatively, K1 can be determined by mathematical analysis of the receiver or by Monte Carlo analysis.
The constant K2 is required to make the slope of the phase discriminator output one at zero phase. This constant is the inverse of the derivative of the equation for the analytical mean of the arctangent function, evaluated at zero carrier phase angle tracking offset and with the tracking loop update rate and signal level such that the standard deviation of the carrier phase angle tracking error is small (i.e., less than 10°). Alternatively, KZ may be determined by mathematical analysis of the receiver or by Monte Carlo analysis.
Once lock is acquired, and thus, the phase angle is known, the inphase signal power, S=, is used as the -normalizing signal instead of ST, since SI has a lower variance than ST within a reasonable carrier phase tracking error range. A summer 88, which is under the control of the microprocessor 24, allows SQ to be added into the SUBSTITUTE SHEET (RULE 26~
WO 97/14052 PCT/CAf6/00614 calculations for the normalizing signal before lock is acquired and inhibits its inclusion after lock is acquired.
Using S= as the normalizing signal effectively lowers the threshold for loss of lock, because of the lower variance. Further, the resulting mean of the phase angle estimate is proportional to tan (~z2), which results on a more linear angle estimation than that produced when ST is used as the normalizing signal.
The receiver uses a DLL, in a conventional manner, to track the L2 P-code by adjusting the phase of the L2 P-code generator 48 to maximize ST~zpp~. This tracking method eliminates the data transmitted over the L2 band. As discussed above, using the arctangent to calculate the phase error estimate results in a 1/2-cycle ambiguity. To reso7_ve this ambiguity without the data bits, a detector 31 compares demodulated code bits from the encrypted L1 and L2 P-codes.
If the L2 P-code bits are inverted, the NCO 46 is adjusted.
Referring now to Fig. 3, the detector 32 compares, in circuit 200, the demodulated bits of the encrypted L1 P-code with the same bits of the encrypted L2 P-code. Delays 202 and 204, respectively, delay the bits from the Ll code and the L2 code, to compensate for differences in signal propagation, and thus, align the bits. The delays 202 anc9 204, which are under the control of the microprocessor 24, are together equal to the phase difference between.the L1 and L2 codes produced by the L1 and L2 P-code generators.
The compare circuit 200 compares the signs of the aligned bits and provides for each set of bits a match or no _ match signal. Based on these signals, a majority vote circuit 206 produces a vote signal that represents by its state whether the majority of bits match or do not match.
The microprocessor 24 periodically samples the vote signal SUBSTITUTE SHEET (RULE 26) and, if the vote signal signifies that the majority of bits do not match, the microprocessor adjusts the NCO 46.
The comparison of the L1 and L2 P-code bits can be made at the P-code rate or at the estimated encryption code rate.
However, the signal strength is greater when the comparisons are made at the narrower bandwidth of the encryption code rate.
Referring also to Fig. 1, the delay 65 should be selected such that it delays the code by a number of chips that is beyond the chip range through which the receiver searches for the L2 P-code. Otherwise, if the locally-generated code and the received signal are out of synchronism by a number of chips that is equal or close to that used in delay 65, the receiver may detect correlation power in the IrrozsE and QNOiss signals when the received signal is multiplied by the delayed code. When this occurs, the Is=c and QS=~ signals, which are produced by multiplying the I and Q signals by a version of the code that is not delayed, and thus, not correlated with the received signal, are noise.
This means that the signals representing the demodulated P-code 'bits" are also noise. When these "bits" are compared, in the detector 32, to the demodulated Ll P-code bits, the result is approximately equal numbers of matches and no matches. This, in turn, results in essentially periodic adjustment of the phase of the NCO 46 by one-half cycle.
If the detector 32 detects equal numbers of matches and no matches, the microprocessor 24 may shift the L2 P-code generator by the number of chips that corresponds to the delay 65. This results in correlation power being detected in the Is=G and Qs=G signals, instead of in the INOxsE and QrroxsE signals. Similarly, if the detector determines that the numbers of matches and no matches vary by relatively small amounts, the microprocessor 24 may shift the code SUBSTITUTE SHEET (RULE 26) generator 48 by an amount that is slightly less than the number of chips that correspond to the delay 65.
The 1/2 cycle detector 32 may also be used to resolve 1/2 cycle ambiguities that arise in receivers that track 'the L2 P-code but use alternative methods to determine the L2 carrier phase. For example, the 1/2 cycle detector may be used in systems that track the L2 P-code and remove it from the signal, and then square the resulting signal to recover the L2 carrier.
Once the receiver is tracking the C/A code and the L1 and L2 P=codes and carriers, it determines the L1 code and phase measurement signals, respectively, from the L1 code and carrier generators 16, 18 and 26 and the L2 code and phase measurements from the L2 code and carrier generators 48 and 46. Using these measurements, the receiver resolves the :full cycle ambiguities, corrects for ionospheric refraction and determines its position. Further, since the L2 code and phase measurements are determined independently from the :G1 measurements, with the exception of the resolution of the 1/2 cycle ambiguity, the receiver can determine carrier-to-noise ratios for each band. It can thus determine the reliability of each of the L1 and L2 signals.
The foregoing description has been limited to a specific embodiment of this invention. It will be apparent, however, that variations and modifications may be made to the invention, with the attainment of some or all of its advantages. Therefore, it is the object of the appended claims to cover all such variations and modifications as come within the true spirit and scope of the invention.
SUBSTITUTE SHEET (RULE 26)
Claims (20)
1. A global position sensing receiver for receiving over L1 and L2 bands, respectively, L1 signals that are modulated by a C/A-code and an encrypted P-code and L2 signals that are modulated by the encrypted P-code, the receiver including:
A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal;
B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code;
C. an L2 carrier angle estimation means for producing an estimate of the phase angle of an L2 carrier;
D. an L2 P-code generator for producing a locally-generated version of the P-code;
E. a controller for controlling the operations of the L2 P-code generator, the controller receiving signals associated with a correlation between the locally-generated P-code and the received L2 signals, and adjusting the L2 P-code generator to align the locally-generated P-code with the L2 signals; and F. a detector for resolving a 1/2-cycle ambiguity in tracking the L2 P-code, the detector including:
i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal;
B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code;
C. an L2 carrier angle estimation means for producing an estimate of the phase angle of an L2 carrier;
D. an L2 P-code generator for producing a locally-generated version of the P-code;
E. a controller for controlling the operations of the L2 P-code generator, the controller receiving signals associated with a correlation between the locally-generated P-code and the received L2 signals, and adjusting the L2 P-code generator to align the locally-generated P-code with the L2 signals; and F. a detector for resolving a 1/2-cycle ambiguity in tracking the L2 P-code, the detector including:
i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
2. The global position sensing receiver of claim 1, wherein the controller receives signals associated with the estimated phase angle of the L2 carrier.
3. The global position sensing receiver of claim 1 wherein the controller determines a carrier phase error estimate as:
where K1 and K2 are constants, I and Q are in phase and quadrature correlation signals, "sign I" represents the sign of the I signal, and S T is an estimate of total signal power, and based on the error estimate adjusts the L2 carrier angle estimation means.
where K1 and K2 are constants, I and Q are in phase and quadrature correlation signals, "sign I" represents the sign of the I signal, and S T is an estimate of total signal power, and based on the error estimate adjusts the L2 carrier angle estimation means.
4. The global position sensing receiver of claim 3 wherein the controller determines total signal power as a sum of a. signal power in an inphase path minus inphase noise components, and b. signal power in a quadrature path minus quadrature noise components.
5. The global position sensing receiver of claim 4 wherein the noise components are determined by a multiplying inphase and quadrature components of the L2 signal by an uncorrelated version of the P-code produced by the L2 P-code generator.
6. The global position sensing receiver of claim 4 wherein the controller, after lock is acquired, substitutes for the estimate of the total signal power the signal power in the inphase path minus noise.
7. The global position sensing receiver of claim 1 wherein the controller, to determine carrier phase tracking error, tracks arctan(Q*signI), where I and Q are inphase and quadrature correlation signals, and based on a determination of the phase error adjusts the L2 carrier angle estimation means.
8. The global position sensing receiver of claim 1 further including means for determining the reliability of the L2 signal by determining an associated carrier-to-noise ratio.
9. A global position sensing receiver for receiving over L1 and L2 bands, respectively, L1 signals that are modulated by a C/A-code and an encrypted P-code and L2 signals that are modulated by the encrypted P-code, the receiver including:
A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal;
B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code;
C. an L2 P-code generator for producing a locally-generated version of the P-code;
D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals;
E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means; and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate as:
where and K1 and K2 are constants, I and Q are inphase and quadrature correlation signals, "sign I" represents the sign of the I signal, and S T is an estimate of total signal power, the controller using the error estimate to adjust the L2 carrier angle estimation means.
A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal;
B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code;
C. an L2 P-code generator for producing a locally-generated version of the P-code;
D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals;
E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means; and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate as:
where and K1 and K2 are constants, I and Q are inphase and quadrature correlation signals, "sign I" represents the sign of the I signal, and S T is an estimate of total signal power, the controller using the error estimate to adjust the L2 carrier angle estimation means.
10. The global position sensing receiver of claim 9 wherein the controller further includes means for determining the reliability of the L2 signals.
11. The global position sensing receiver of claim 10 wherein the controller determines total signal power as a sum of a. signal power in an inphase path minus inphase noise components, and b. signal power in a quadrature path minus quadrature noise components.
12. The global position sensing receiver of claim 11 wherein the noise components are determined by multiplying inphase and quadrature components of the L2 signal by an uncorrelated version of the P-code produced by the L2 P-code generator.
13. The global position sensing receiver of claim 11 wherein the controller, after lock is acquired, substitutes for the estimate of the total signal power the signal power in the inphase path minus inphase noise components.
14. The global position sensing receiver of claim 9 wherein the controller, to determine carrier phase tracking error, tracks the product arctan(Q*signI), where I and Q are inphase and quadrature correlation signals.
15. The global position sensing receiver of claim 14 further including a detector for resolving a 1/2-cycle ambiguity in tracking the L2 P-code, the detector including:
i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
16. A global position sensing receiver for receiving over L1 and L2 bands, respectively, L1 signals that are modulated both by a C/A-code and a P-code that is, at times, encrypted, and L2 signals that are modulated by the P-code that is, at times, encrypted, the receiver including:
A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal;
B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code;
C. an L2 P-code generator for producing a locally-generated version of the P-code;
D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals;
E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means; and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate based on an estimate of total signal power, S T, which is determined as a sum of a. signal power in an inphase path minus inphase noise components, and b. signal power in a quadrature path minus quadrature noise components, the controller using the error estimate to adjust the L2 carrier angle estimation means.
A. means for producing a locally-generated version of the C/A-code that is aligned with the C/A-code in the received L1 signal;
B. an L1 P-code generator for producing a locally-generated version of the P-code that is phase-locked to the locally-generated version of the C/A-code;
C. an L2 P-code generator for producing a locally-generated version of the P-code;
D. correlation means for determining how closely the P-code produced by the L2 P-code generator and the P-code in the L2 signal are aligned, said means producing L2 correlation signals;
E. L2 carrier angle estimation means for providing an estimate of a carrier phase angle based on the correlation signals produced by the correlation means; and F. a controller for controlling the operations of the L2 P-code generator and the L2 carrier angle estimation means, the controller receiving signals from the correlation means and the L2 carrier angle estimate means, and adjusting the L2 P-code generator, to align the locally-generated P-code with the L2 signals, and adjusting the L2 carrier angle estimation means to phase lock said means to the L2 signal, the controller determining a carrier phase error estimate based on an estimate of total signal power, S T, which is determined as a sum of a. signal power in an inphase path minus inphase noise components, and b. signal power in a quadrature path minus quadrature noise components, the controller using the error estimate to adjust the L2 carrier angle estimation means.
17. The global position sensing receiver of claim 16 wherein the noise components are determined by multiplying inphase and quadrature components of the L2 signal by an uncorrelated version of the P-code produced by the L2 P-code generator.
18. The global position sensing receiver of claim 17 wherein the controller determines a carrier phase error estimate as:
where K1 and K2 are constants, I and Q are inphase and quadrature correlation signals, "sign I" represents the sign of the I signal.
where K1 and K2 are constants, I and Q are inphase and quadrature correlation signals, "sign I" represents the sign of the I signal.
19. The global position sensing receiver of claims 16 and 18 wherein the controller, after lock is acquired, substitutes for the estimate of the total signal power the signal power in the inphase path minus inphase noise components.
20. The global position sensing receiver of claim 16 further including a detector for resolving a 1/2-cycle ambiguity in tracking the L2 P-code, the detector including:
i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
i. a majority vote circuit for determining if a majority of the bits in the L2 P-code match or do not match corresponding bits of the L1 P-code, and ii. means for adjusting the carrier angle estimation means if the majority vote circuit determines that a majority of the L1 and L2 bits do not match.
Applications Claiming Priority (3)
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| US08/540,076 US5736961A (en) | 1995-10-06 | 1995-10-06 | Dual Frequency global positioning system |
| US08/540,076 | 1995-10-06 | ||
| PCT/CA1996/000614 WO1997014052A1 (en) | 1995-10-06 | 1996-09-17 | Dual frequency global positioning system |
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| CA2207073A1 CA2207073A1 (en) | 1997-04-17 |
| CA2207073C true CA2207073C (en) | 2003-08-12 |
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| EP (1) | EP0796437B1 (en) |
| JP (1) | JP3117465B2 (en) |
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Families Citing this family (48)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5825887A (en) * | 1995-12-28 | 1998-10-20 | Trimble Navigation Limited | Transmitting and receiving apparatus for full code correlation operation under encryption for satellite positioning system |
| US6289041B1 (en) | 1997-02-11 | 2001-09-11 | Snaptrack, Inc. | Fast Acquisition, high sensitivity GPS receiver |
| US5883597A (en) * | 1997-11-17 | 1999-03-16 | Rockwell International | Frequency translation method and circuit for use in GPS antenna electronics |
| ATE323890T1 (en) * | 1997-11-19 | 2006-05-15 | Imec Vzw | METHOD AND DEVICE FOR RECEIVING GPS/GLONASS SIGNALS |
| FR2771867B1 (en) * | 1997-12-03 | 2000-02-04 | Dassault Sercel Navigation Pos | BI-FREQUENCY GPS RECEIVER, OPERATIVE ON ALL MEASUREMENTS IN THE PRESENCE OF ENCRYPTION |
| US6208291B1 (en) * | 1998-05-29 | 2001-03-27 | Snaptrack, Inc. | Highly parallel GPS correlator system and method |
| US6184822B1 (en) | 1998-08-24 | 2001-02-06 | Novatel, Inc. | Split C/A code receiver |
| FR2783929B1 (en) * | 1998-09-25 | 2000-12-08 | Sextant Avionique | PROCESS AND DEVICE FOR PROCESSING IN RECEPTION OF A GPS SATELLITE L2 SIGNAL |
| US6125135A (en) * | 1998-11-25 | 2000-09-26 | Navcom Technology, Inc. | System and method for demodulating global positioning system signals |
| GB9928356D0 (en) * | 1999-12-01 | 2000-01-26 | Koninkl Philips Electronics Nv | Method and apparatus for code phase correlation |
| US6735242B1 (en) * | 1999-08-30 | 2004-05-11 | Nokia Corporation | Time tracking loop for pilot aided direct sequence spread spectrum systems |
| WO2001057549A2 (en) * | 2000-01-24 | 2001-08-09 | Integrinautics Corporation | Multi-frequency pseudolites for carrier-based differential-position determination |
| EP1309878A4 (en) | 2000-06-23 | 2005-01-05 | Sportvision Inc | Track model constraint for gps position |
| AU2001272980A1 (en) | 2000-06-23 | 2002-01-08 | Sportvision, Inc. | Gps based tracking system |
| US6525688B2 (en) * | 2000-12-04 | 2003-02-25 | Enuvis, Inc. | Location-determination method and apparatus |
| US6731239B2 (en) * | 2002-01-18 | 2004-05-04 | Ford Motor Company | System and method for retrieving information using position coordinates |
| AU2003230170A1 (en) * | 2002-05-15 | 2003-12-02 | Cellguide | Sensitive gps receiver |
| US7197102B2 (en) * | 2002-06-07 | 2007-03-27 | International Business Machines Corporation | Method and apparatus for clock-and-data recovery using a secondary delay-locked loop |
| US6753810B1 (en) * | 2002-09-24 | 2004-06-22 | Navcom Technology, Inc. | Fast ambiguity resolution for real time kinematic survey and navigation |
| US6922167B2 (en) | 2003-07-14 | 2005-07-26 | European Space Agency | Hardware architecture for processing galileo alternate binary offset carrier (AltBOC) signals |
| US6934632B2 (en) * | 2003-10-08 | 2005-08-23 | Navcom Technology, Inc. | Method for using three GPS frequencies to resolve carrier-phase integer ambiguities |
| US7432853B2 (en) * | 2003-10-28 | 2008-10-07 | Trimble Navigation Limited | Ambiguity estimation of GNSS signals for three or more carriers |
| ATE400823T1 (en) * | 2004-10-01 | 2008-07-15 | Nokia Corp | DUAL FREQUENCY RECEPTION OF SPREAD SPECTRUM SIGNALS |
| CN101287999B (en) * | 2005-10-03 | 2011-11-02 | 天宝导航有限公司 | Multiple-gnss and fdma high precision carrier-phase based positioning |
| US7480580B2 (en) * | 2005-10-18 | 2009-01-20 | Schweitzer Engineering Laboratories, Inc. | Apparatus and method for estimating synchronized phasors at predetermined times referenced to an absolute time standard in an electrical system |
| CN1869730B (en) * | 2006-06-26 | 2010-07-14 | 威盛电子股份有限公司 | Global locator system signal receiver and its searching and capturing method |
| DE102006029486A1 (en) * | 2006-06-27 | 2008-01-03 | Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V. | Signal conditioner and method for processing a received signal |
| GB0615930D0 (en) * | 2006-08-10 | 2006-09-20 | Univ Surrey | A receiver of binary offset carrier modulated signals |
| US8442020B1 (en) | 2006-09-12 | 2013-05-14 | Rockwell Collins, Inc. | Phase compensation system and method to correct M-code dual sideband distortion |
| US7630863B2 (en) * | 2006-09-19 | 2009-12-08 | Schweitzer Engineering Laboratories, Inc. | Apparatus, method, and system for wide-area protection and control using power system data having a time component associated therewith |
| US7633437B2 (en) * | 2006-09-22 | 2009-12-15 | Navcom Technology, Inc. | Method for using three GPS frequencies to resolve whole-cycle carrier-phase ambiguities |
| FR2914430B1 (en) * | 2007-03-29 | 2011-03-04 | Centre Nat Detudes Spatiales Cnes | PROCESS FOR PROCESSING RADIONAVIGATION SIGNALS. |
| MX2010002163A (en) * | 2007-09-28 | 2010-06-02 | Schweitzer Engineering Lab Inc | Amplitude and phase comparators for line protection. |
| CA2700973C (en) * | 2007-09-28 | 2014-05-13 | Schweitzer Engineering Laboratories, Inc. | Systems and methods for power swing and out-of-step detection using time stamped data |
| US20090088990A1 (en) * | 2007-09-30 | 2009-04-02 | Schweitzer Iii Edmund O | Synchronized phasor processor for a power system |
| US8494795B2 (en) * | 2008-05-05 | 2013-07-23 | Schweitzer Engineering Laboratories Inc | Apparatus and method for estimating synchronized phasors at predetermined times referenced to a common time standard in an electrical system |
| CN101539619B (en) * | 2009-03-19 | 2011-09-07 | 北京理工大学 | Carrier wave aided tracking method used in high-dynamic double frequency GPS |
| CN101710180A (en) * | 2009-11-09 | 2010-05-19 | 上海华测导航技术有限公司 | Structure of base band circuit for realizing double frequency GPS satellite signal receiver and method thereof |
| CN102116866B (en) * | 2009-12-31 | 2013-01-23 | 和芯星通科技(北京)有限公司 | Method and device for tracking global positioning system precision (GPS P) and/or Y code signal of full-cycle carrier |
| GB2488354A (en) * | 2011-02-24 | 2012-08-29 | Salford Electronic Consultants Ltd | Measuring the shape of a boom using single and dual frequency GPS receivers |
| CN103308064B (en) * | 2013-05-20 | 2015-10-28 | 广州番禺巨大汽车音响设备有限公司 | A kind of method and system realizing vehicle tablet terminal location information service |
| US8960019B1 (en) | 2014-06-11 | 2015-02-24 | Gilbarco Inc. | Fuel dispenser time synchronization and geotracking |
| US9568516B2 (en) | 2014-09-23 | 2017-02-14 | Schweitzer Engineering Laboratories, Inc. | Determining status of electric power transmission lines in an electric power transmission system |
| CN104931980B (en) * | 2015-03-10 | 2017-04-05 | 中国电子科技集团公司第十研究所 | Carrier phase measurement half cycle obscures release method |
| CN105607084B (en) * | 2015-09-09 | 2019-06-18 | 湖南北云科技有限公司 | A kind of high-precision direction-finding receiver carrier wave half cycle transition detection device and method |
| CN105572710B (en) * | 2015-12-18 | 2017-09-29 | 深圳市力合微电子股份有限公司 | The method for improving the positioning precision of the civilian double frequency location receiver of Beidou II |
| US11262458B2 (en) * | 2018-04-04 | 2022-03-01 | The Regents Of The University Of Colorado, A Body Corporate | Smart antenna module for GNSS receivers |
| US11009609B2 (en) | 2018-07-17 | 2021-05-18 | Spire Global, Inc. | Systems and methods for de-noising GNSS signals |
Family Cites Families (23)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4485383A (en) * | 1980-12-01 | 1984-11-27 | Texas Instruments Incorporated | Global position system (GPS) multiplexed receiver |
| US4870422A (en) * | 1982-03-01 | 1989-09-26 | Western Atlas International, Inc. | Method and system for determining position from signals from satellites |
| US4860018A (en) * | 1982-03-01 | 1989-08-22 | Western Atlas International, Inc. | Continuous wave interference rejection for reconstructed carrier receivers |
| US4894662A (en) * | 1982-03-01 | 1990-01-16 | Western Atlas International, Inc. | Method and system for determining position on a moving platform, such as a ship, using signals from GPS satellites |
| US4667203A (en) * | 1982-03-01 | 1987-05-19 | Aero Service Div, Western Geophysical | Method and system for determining position using signals from satellites |
| US4809005A (en) * | 1982-03-01 | 1989-02-28 | Western Atlas International, Inc. | Multi-antenna gas receiver for seismic survey vessels |
| US4797677A (en) * | 1982-10-29 | 1989-01-10 | Istac, Incorporated | Method and apparatus for deriving pseudo range from earth-orbiting satellites |
| US4841544A (en) * | 1987-05-14 | 1989-06-20 | The Charles Stark Draper Laboratory, Inc. | Digital direct sequence spread spectrum receiver |
| US4821294A (en) * | 1987-07-08 | 1989-04-11 | California Institute Of Technology | Digital signal processor and processing method for GPS receivers |
| US4862178A (en) * | 1988-06-27 | 1989-08-29 | Litton Systems, Inc. | Digital system for codeless phase measurement |
| US4928106A (en) * | 1988-07-14 | 1990-05-22 | Ashtech Telesis, Inc. | Global positioning system receiver with improved radio frequency and digital processing |
| US4972431A (en) * | 1989-09-25 | 1990-11-20 | Magnavox Government And Industrial Electronics Company | P-code-aided global positioning system receiver |
| US5073907A (en) * | 1990-01-30 | 1991-12-17 | California Institute Of Technology | Digital phase-lock loop |
| US5390207A (en) * | 1990-11-28 | 1995-02-14 | Novatel Communications Ltd. | Pseudorandom noise ranging receiver which compensates for multipath distortion by dynamically adjusting the time delay spacing between early and late correlators |
| US5101416A (en) * | 1990-11-28 | 1992-03-31 | Novatel Comunications Ltd. | Multi-channel digital receiver for global positioning system |
| US5245628A (en) * | 1991-03-29 | 1993-09-14 | Texas Instruments Incorporated | Enhanced l1/l2 code channel for global positioning system receivers |
| US5134407A (en) * | 1991-04-10 | 1992-07-28 | Ashtech Telesis, Inc. | Global positioning system receiver digital processing technique |
| US5414729A (en) * | 1992-01-24 | 1995-05-09 | Novatel Communications Ltd. | Pseudorandom noise ranging receiver which compensates for multipath distortion by making use of multiple correlator time delay spacing |
| US5576715A (en) * | 1994-03-07 | 1996-11-19 | Leica, Inc. | Method and apparatus for digital processing in a global positioning system receiver |
| US5535278A (en) * | 1994-05-02 | 1996-07-09 | Magnavox Electronic Systems Company | Global positioning system (GPS) receiver for recovery and tracking of signals modulated with P-code |
| US5621416A (en) * | 1995-02-02 | 1997-04-15 | Trimble Navigation Limited | Optimized processing of signals for enhanced cross-correlation in a satellite positioning system receiver |
| US5615236A (en) * | 1995-03-29 | 1997-03-25 | Trimble Navigation Limited | Method and apparatus for direct re-acquisition of precision-code after a short power interruption |
| US5610984A (en) * | 1995-11-22 | 1997-03-11 | Trimble Navigation Limited | Optimal L2 tracking in a SPS receiver under encryption without knowledge of encryption timing characteristics |
-
1995
- 1995-10-06 US US08/540,076 patent/US5736961A/en not_active Expired - Lifetime
-
1996
- 1996-09-17 CN CN96191598A patent/CN1096611C/en not_active Expired - Lifetime
- 1996-09-17 JP JP09514582A patent/JP3117465B2/en not_active Expired - Lifetime
- 1996-09-17 CA CA002207073A patent/CA2207073C/en not_active Expired - Lifetime
- 1996-09-17 EP EP96929989A patent/EP0796437B1/en not_active Expired - Lifetime
- 1996-09-17 DE DE69605279T patent/DE69605279T2/en not_active Expired - Lifetime
- 1996-09-17 WO PCT/CA1996/000614 patent/WO1997014052A1/en active IP Right Grant
- 1996-09-17 AU AU69209/96A patent/AU715461B2/en not_active Expired
-
1998
- 1998-03-12 HK HK98102049A patent/HK1002970A1/en not_active IP Right Cessation
Also Published As
| Publication number | Publication date |
|---|---|
| CN1096611C (en) | 2002-12-18 |
| DE69605279T2 (en) | 2000-06-15 |
| CA2207073A1 (en) | 1997-04-17 |
| EP0796437A1 (en) | 1997-09-24 |
| WO1997014052A1 (en) | 1997-04-17 |
| AU6920996A (en) | 1997-04-30 |
| HK1002970A1 (en) | 1998-09-30 |
| DE69605279D1 (en) | 1999-12-30 |
| AU715461B2 (en) | 2000-02-03 |
| JPH10510632A (en) | 1998-10-13 |
| EP0796437B1 (en) | 1999-11-24 |
| US5736961A (en) | 1998-04-07 |
| CN1172531A (en) | 1998-02-04 |
| JP3117465B2 (en) | 2000-12-11 |
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